AD8610ARZ应用文章市场行情现货热卖使用介绍供应商报价-中国IC网-芯三七

Precision, Very Low Noise,

Low Input Bias Current, Wide Bandwidth

JFET Operational Amplifier

AD8610/AD8620

FEATURES

FUNCTIONAL BLOCK DIAGRAMS

Low Noise 6 nV/√Hz

Low Offset Voltage: 100 ␮V Max

Low Input Bias Current 10 pA Max

Fast Settling: 600 ns to 0.01%

Low Distortion

8-Lead MSOP and SOIC

(RM-8 and R-8 Suffixes)

1

8

NULL

؊IN

؉IN

V؊

NC

V؉

OUT

NULL

AD8610

Unity Gain Stable

4

5

No Phase Reversal

Dual-Supply Operation: ؎5 V to ؎13 V

NC = NO CONNECT

8-Lead SOIC

(R-8 Suffix)

APPLICATIONS

Photodiode Amplifier

ATE

1

8

OUTA

؊INA

؉INA

V؊

V؉

OUTB

؊INB

؉INB

Instrumentation

AD8620

Sensors and Controls

High Performance Filters

Fast Precision Integrators

High Performance Audio

4

5

GENERAL DESCRIPTION

AD8610/AD8620 is an ideal amplifier for driving high performance

A/D inputs and buffering D/A converter outputs.

The AD8610/AD8620 is a very high precision JFET input amplifier

featuring ultralow offset voltage and drift, very low input voltage

and current noise, very low input bias current, and wide bandwidth.

Unlike many JFET amplifiers, the AD8610/AD8620 input bias

current is low over the entire operating temperature range. The

AD8610/AD8620 is stable with capacitive loads of over 1000 pF

in noninverting unity gain; much larger capacitive loads can be

driven easily at higher noise gains. The AD8610/AD8620 swings to

within 1.2 V of the supplies even with a 1 kΩ load, maximizing

dynamic range even with limited supply voltages. Outputs slew at

50 V/µs in either inverting or noninverting gain configurations, and

settle to 0.01% accuracy in less than 600 ns. Combined with the

high input impedance, great precision, and very high output drive, the

Applications for the AD8610/AD8620 include electronic instru-

ments; ATE amplification, buffering, and integrator circuits;

CAT/MRI/ultrasound medical instrumentation; instrumentation

quality photodiode amplification; fast precision filters (including

PLL filters); and high quality audio.

The AD8610/AD8620 is fully specified over the extended

industrial (–40°C to +125°C) temperature range. The AD8610

is available in the narrow 8-lead SOIC and the tiny MSOP8

surface-mount packages. The AD8620 is available in the narrow

8-lead SOIC package. MSOP8 packaged devices are available

only in tape and reel.

REV. D

Information furnished by Analog Devices is believed to be accurate and

reliable. However, no responsibility is assumed by Analog Devices for its

use, norforanyinfringementsofpatentsorotherrightsofthirdpartiesthat

may result from its use. No license is granted by implication or otherwise

under any patent or patent rights of Analog Devices. Trademarks and

registered trademarks are the property of their respective owners.

One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.

Tel: 781/329-4700

Fax: 781/326-8703

www.analog.com

(@ V = ؎5.0 V, V_CM= 0 V, T_A= 25؇C, unless otherwise noted.)

AD8610/AD8620–SPECIFICATIONS

S

Parameter

Symbol

Conditions

Min

Typ

Max

Unit

INPUT CHARACTERISTICS

Offset Voltage (AD8610B)

V_OS

45

80

45

80

85

90

150

+2

+130

+1.5

+1

100

200

150

300

250

350

850

+10

+250

+2.5

+10

+75

+150

+3

µV

–40°C < T_A< +125°C

µV

Offset Voltage (AD8620B)

µV

Offset Voltage (AD8610A/AD8620A)

µV

+25°C < T_A< 125°C

–40°C < T_A< +125°C

µV

Input Bias Current

Input Offset Current

I_B

–10

–250

–2.5

–10

–75

–150

–2

pA

–40°C < T_A< +85°C

–40°C < T_A< +125°C

pA

nA

pA

V

I_OS

–40°C < T_A< +85°C

–40°C < T_A< +125°C

+20

+40

Input Voltage Range

Common-Mode Rejection Ratio

Large Signal Voltage Gain

Offset Voltage Drift (AD8610B)

Offset Voltage Drift (AD8620B)

Offset Voltage Drift (AD8610A/AD8620A)

CMRR

A_VO

∆V_OS/∆T

V_CM= –2.5 V to +1.5 V

R_L= 1 kΩ, V_O= –3 V to +3 V

–40°C < T_A< +125°C

90

100

95

dB

180

0.5

0.8

V/mV

µV/°C

1

1.5

3.5

OUTPUT CHARACTERISTICS

Output Voltage High

Output Voltage Low

V_OH

V_OL

I_OUT

R_L= 1 kΩ, –40°C < T_A< +125°C

3.8

100

40

4

–4

30

V

mA

–3.8

Output Current

V_OUT

>

2 V

POWER SUPPLY

Power Supply Rejection Ratio

Supply Current/Amplifier

PSRR

I_SY

V_S= 5 V to 13 V

V_O= 0 V

–40°C < T_A< +125°C

110

2.5

3.0

dB

mA

3.0

3.5

DYNAMIC PERFORMANCE

Slew Rate

Gain Bandwidth Product

Settling Time

SR

GBP

t_S

R_L= 2 kΩ

50

25

350

V/µs

MHz

ns

A_V= +1, 4 V Step, to 0.01%

NOISE PERFORMANCE

Voltage Noise

Voltage Noise Density

Current Noise Density

Input Capacitance

Differential

Common-Mode

Channel Separation

f = 10 kHz

e_np-p

e_n

i_n

0.1 Hz to 10 Hz

f = 1 kHz

1.8

6

5

µV p-p

nV/

√

Hz

fA/√

Hz

C_IN

8

15

pF

C_S

137

120

dB

f = 300 kHz

Specifications subject to change without notice.

–2–

REV. D

AD8610/AD8620

ELECTRICAL SPECIFICATIONS (@ V_S= ؎13 V, V_CM= 0 V, T_A= 25؇C, unless otherwise noted.)

Parameter

Symbol

Conditions

Min

Typ

Max

Unit

INPUT CHARACTERISTICS

Offset Voltage (AD8610B)

V_OS

45

80

45

80

85

90

150

+3

+130

100

200

150

300

250

350

850

+10

+250

+3.5

+10

+75

+150

+10.5

µV

–40°C < T_A< +125°C

µV

Offset Voltage (AD8620B)

µV

Offset Voltage (AD8610A/AD8620A)

µV

+25°C < T_A< 125°C

–40°C < T_A< +125°C

µV

Input Bias Current

Input Offset Current

I_B

–10

pA

–40°C < T_A< +85°C

–40°C < T_A< +125°C

–250

–3.5

–10

pA

nA

pA

V

dB

V/mV

µV/°C

I_OS

+1.5

+20

+40

–40°C < T_A< +85°C

–40°C < T_A< +125°C

–75

–150

–10.5

90

Input Voltage Range

Common-Mode Rejection Ratio

Large Signal Voltage Gain

Offset Voltage Drift (AD8610B)

Offset Voltage Drift (AD8620B)

CMRR

A_VO

∆V_OS/∆T

V_CM= –10 V to +10 V

R_L= 1 kΩ, V_O= –10 V to +10 V

–40°C < T_A< +125°C

110

200

0.5

0.8

100

1

1.5

3.5

Offset Voltage Drift (AD8610A/AD8620A) ∆V_OS/∆T

OUTPUT CHARACTERISTICS

Output Voltage High

Output Voltage Low

Output Current

V_OH

V_OL

I_OUT

I_SC

R_L= 1 kΩ, –40°C < T_A< +125°C

V_OUT> 10 V

+11.75 +11.84

V

mA

–11.84 –11.75

45

65

Short Circuit Current

POWER SUPPLY

Power Supply Rejection Ratio

Supply Current/Amplifier

PSRR

I_SY

V_S= 5 V to 13 V

V_O= 0 V

–40°C < T_A< +125°C

100

40

110

3.0

3.5

dB

mA

3.5

4.0

DYNAMIC PERFORMANCE

Slew Rate

Gain Bandwidth Product

Settling Time

SR

GBP

t_S

R_L= 2 kΩ

60

25

600

V/µs

MHz

ns

A_V= 1, 10 V Step, to 0.01%

NOISE PERFORMANCE

Voltage Noise

Voltage Noise Density

Current Noise Density

Input Capacitance

Differential

Common-Mode

Channel Separation

f = 10 kHz

e_np-p

e_n

i_n

0.1 Hz to 10 Hz

f = 1 kHz

1.8

6

5

µV p-p

nV/

√

Hz

fA/√

Hz

C_IN

8

15

pF

C_S

137

120

dB

f = 300 kHz

Specifications subject to change without notice.

REV. D

–3–

AD8610/AD8620

ABSOLUTE MAXIMUM RATINGS*

Package Type

␪_JA*

␪

Unit

JC

Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27.3 V

Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . V_S––to V_S+

Differential Input Voltage . . . . . . . . . . . . . . . Supply Voltage

Output Short-Circuit Duration to GND . . . . . . . . . . Indefinite

Storage Temperature Range

8-Lead MSOP (RM)

8-Lead SOIC (RN)

190

158

44

43

°C/W

*θ_JAis specified for worst-case conditions; i.e., θ_JAis specified for a device

soldered in circuit board for surface-mount packages.

R, RM Packages . . . . . . . . . . . . . . . . . . . . . –65°C to +150°C

Operating Temperature Range

AD8610/AD8620 . . . . . . . . . . . . . . . . . . . . –40°C to +125°C

Junction Temperature Range

R, RM Packages . . . . . . . . . . . . . . . . . . . . . –65°C to +150°C

Lead Temperature Range (Soldering, 10 sec) . . . . . . . . 300°C

*Stresses above those listed under Absolute Maximum Ratings may cause permanent

damage to the device. This is a stress rating only; functional operation of the device

at these or any other conditions above those listed in the operational sections of this

specification is not implied. Exposure to absolute maximum rating conditions for

extended periods may affect device reliability.

ORDERING GUIDE

Temperature

Range

Package

Description

Package

Option

Model

Branding

AD8610AR

–40°C to +125°C 8-Lead SOIC

RN-8

AD8610AR-REEL

AD8610AR-REEL7

AD8610ARM-REEL

AD8610ARM-R2

AD8610ARZ*

AD8610ARZ-REEL*

AD8610ARZ-REEL7* –40°C to +125°C 8-Lead SOIC

AD8610BR

AD8610BR-REEL

AD8610BR-REEL7

AD8610BRZ*

AD8610BRZ-REEL*

AD8610BRZ-REEL7* –40°C to +125°C 8-Lead SOIC

AD8620AR

–40°C to +125°C 8-Lead MSOP RM-8

B0A

–40°C to +125°C 8-Lead MSOP RM-8

–40°C to +125°C 8-Lead SOIC

RN-8

–40°C to +125°C 8-Lead SOIC

AD8620AR-REEL

AD8620AR-REEL7

AD8620BR

AD8620BR-REEL

AD8620BR-REEL7

*Pb-free part

CAUTION

ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily

accumulate on the human body and test equipment and can discharge without detection. Although the

AD8610/AD8620 features proprietary ESD protection circuitry, permanent damage may occur on

devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are

recommended to avoid performance degradation or loss of functionality.

–4–

REV. D

Typical Performance Characteristics–AD8610/AD8620

14

12

10

8

600

18

16

14

12

10

8

V

= ؎5V

S

V

= ؎13V

V

= ؎13V

S

400

200

0

6

؊200

؊400

6

4

2

؊600

0

25

85

125

؊40

؊250 ؊150

INPUT OFFSETVOLTAGE – ␮V

؊50

50

150

250

؊250 ؊150

؊50

50

150

250

TEMPERATURE – ؇C

INPUT OFFSETVOLTAGE – ␮V

TPC 1. Input Offset Voltage at 13 V

TPC 2. Input Offset Voltage vs.

TPC 3. Input Offset Voltage at 5 V

Temperature at 13 V (300 Amplifiers)

3.6

600

14

V = ؎13V

S

V

S

= ؎5V OR ؎13V

V

= ؎5V

S

3.4

3.2

3.0

2.8

2.6

2.4

2.2

2.0

12

10

8

400

200

0

6

–200

–400

–600

4

2

0

–40

25

85

125

0

5

10

؊10

؊5

COMMON-MODEVOLTAGE –V

0

0.2

0.6

1.0

1.4

– ␮V/؇C

1.8

2.2

2.6

TEMPERATURE – ؇C

T V

C OS

TPC 4. Input Offset Voltage vs.

Temperature at 5 V (300 Amplifiers)

TPC 5. Input Offset Voltage Drift

TPC 6. Input Bias Current vs.

Common-Mode Voltage

3.05

3.0

2.5

2.0

1.5

1.0

0.5

0

2.65

2.60

2.55

2.50

2.45

2.40

2.35

2.30

V

= ؎13V

V

= ؎5V

S

2.95

2.85

2.75

2.65

2.55

0

1

2

3

4

5

6

7

8

9

10 11 12 13

25

85

125

؊40

25

85

125

؊40

SUPPLYVOLTAGE – ؎V

TEMPERATURE – ؇C

TPC 8. Supply Current vs.

Temperature at 13 V

TPC 7. Supply Current vs.

Supply Voltage

TPC 9. Supply Current vs.

Temperature at 5 V

REV. D

–5–

AD8610/AD8620

1.8

4.25

4.20

4.15

4.10

4.05

4.00

3.95

؊3.95

؊4.00

؊4.05

؊4.10

؊4.15

؊4.20

؊4.25

؊4.30

V

R

= ؎5V

= 1k⍀

S

V

= ؎13V

V

R

= ؎5V

= 1k⍀

S

1.6

L

1.4

1.2

1.0

0.8

0.6

0.4

0.2

0

25

85

125

100

1k

10k

100k

1M

10M 100M

؊40

25

85

125

؊40

TEMPERATURE – ؇C

RESISTANCE LOAD –⍀

TPC 12. Output Voltage Low vs.

Temperature at 5 V

TPC 10. Output Voltage to

Supply Rail vs. Load

TPC 11. Output Voltage High vs.

Temperature at 5 V

120

100

80

12.05

12.00

11.95

270

225

180

135

90

؊11.80

؊11.85

؊11.90

؊11.95

؊12.00

؊12.05

V

R

= ؎13V

= 1k⍀

V

R

= ؎13V

= 1k⍀

S

V

R

= ؎13V

= 1k⍀

S

L

MARKER AT 27MHz

␪

M

= 69.5

= 20pF

C

60

L

40

20

45

11.90

0

؊20

؊40

؊60

؊80

؊45

؊90

؊135

؊180

11.85

11.80

25

85

125

؊40

10

1

100 200

25

85

125

؊40

TEMPERATURE – ؇C

FREQUENCY – MHz

TEMPERATURE – ؇C

TPC 13. Output Voltage High

vs. Temperature at 13 V

TPC 15. Open-Loop Gain

and Phase vs. Frequency

TPC 14. Output Voltage Low vs.

Temperature at 13 V

60

190

180

170

160

150

140

130

120

110

100

260

V

R

C

= ؎13V

= 2k⍀

= 20pF

S

V

R

= ؎13V

= ؎10V

= 1k⍀

S

V

R

= ؎5V

= ؎3V

= 1k⍀

S

L

240

220

O

40

20

L

G = 100

G = 10

G = 1

200

180

0

160

140

120

100

؊20

؊40

25

85

125

25

85

125

؊40

1k

10k

100k

1M

10M

100M

TEMPERATURE – ؇C

FREQUENCY – Hz

TEMPERATURE – ؇C

TPC 16. Closed-Loop Gain vs.

Frequency

TPC 17. A_VOvs. Temperature at 13 V

TPC 18. A_VOvs. Temperature at 5 V

–6–

REV. D

AD8610/AD8620

160

140

120

160

140

122

121

V

S

= ؎13V

V = ؎5V

S

120

100

80

60

40

20

0

100

80

60

40

20

0

+PSRR

120

119

118

117

116

+PSRR

–PSRR

–20

–40

–20

–40

100

1k

10k

100k

1M

10M

60M

100

1k

10k

100k

1M

10M 60M

؊40

125

25

85

FREQUENCY – Hz

TEMPERATURE – ؇C

TPC 19. PSRR vs. Frequency at 13 V

TPC 21. PSRR vs. Temperature

TPC 20. PSRR vs. Frequency at 5 V

140

V

= ؎13V

= 300mV p-p

= ؊100

= 10k⍀

= 0pF

S

V

S

= ؎13V

V

= ؎13V

= ؊300mV p-p

= ؊100

S

V

IN

120

100

80

V

IN

A

R

C

V

L

A

R

V

L

= 10k⍀

V

IN

0V

V

60

IN

V

OUT

40

CH = 5V/DIV

2

V

OUT

20

0

CH = 5V/DIV

2

10

100

1k

10k 100k 1M 10M 60M

TIME – 4␮s/DIV

FREQUENCY – Hz

TPC 22. CMRR vs. Frequency

TPC 24. Negative Overvoltage

Recovery

TPC 23. Positive Overvoltage Recovery

100

1,000

V = ؎13V

S

V

SY

= ؎13V

V

= ؎13V

p-p = 1.8␮V

S

90

80

70

60

50

40

30

20

10

0

IN

100

10

1

GAIN = 1

GAIN = 10

GAIN = 100

TIME – 1s/DIV

1

10

100

1k

10k

100k

1M

1k

10k

100k

1M

10M

100M

FREQUENCY – Hz

TPC 25. 0.1 Hz to 10 Hz Input Voltage

Noise

TPC 26. Input Voltage Noise vs.

Frequency

TPC 27. Z_OUTvs. Frequency

REV. D

–7–

AD8610/AD8620

100

90

80

70

60

50

40

35

30

25

20

15

10

5

3000

2500

2000

1500

1000

500

V

= ؎5V

V

S

= ؎13V

S

R

L

= 2k⍀

V

IN

= 100mV p-p

GAIN = 1

GAIN = 10

+OS

؊OS

30

20

10

0

GAIN = 100

0

25

85

125

1

10

100

CAPACITANCE – pF

1k

10k

1k

10k

100k

1M

10M

100M

TEMPERATURE – ؇C

FREQUENCY – Hz

TPC 29. Input Bias Current vs.

Temperature

TPC 28. Z_OUTvs. Frequency

TPC 30. Small Signal Overshoot vs.

Load Capacitance

40

35

30

25

20

15

10

5

V

= ؎13V

= ؎14V

= +1

S

V

R

= ؎5V

= 2k⍀

= 100mV

S

V

IN

L

A

V

IN

FREQ = 0.5kHz

V

IN

+OS

؊OS

V

= ؎13V

p-p = 20V

= +1

= 2k⍀

= 20pF

V

OUT

S

V

IN

A

R

C

V

L

0

TIME – 400␮s/DIV

1

10

100

CAPACITANCE – pF

1k

10k

TIME – 1␮s/DIV

TPC 32. No Phase Reversal

TPC 33. Large Signal Response at

G = +1

TPC 31. Small Signal Overshoot vs.

Load Capacitance

V

= ؎13V

p-p = 20V

= +1

= 2k⍀

= 20pF

S

V

A

R

C

= ؎13V

p-p = 20V

= ؊1

= 2k⍀

= 20pF

V

A

R

C

= ؎13V

p-p = 20V

= +1

= 2k⍀

= 20pF

S

V

IN

A

R

C

V

L

V

L

V

L

TIME – 400ns/DIV

TIME – 1␮s/DIV

TPC 35. –SR at G = +1

TPC 34. +SR at G = +1

TPC 36. Large Signal Response at G = –1

–8–

REV. D

AD8610/AD8620

V

= ؎13V

p-p = 20V

= ؊1

S

V

IN

A

V

R

L

= 2k⍀

SR = 50V/␮s

= 20pF

C

L

V

= ؎13V

p-p = 20V

= ؊1

S

V

IN

A

V

R

L

= 2k⍀

SR = 55V/␮s

= 20pF

C

L

TIME – 400ns/DIV

TPC 37. +SR at G = –1

TPC 38. –SR at G = –1

CS(dB) = 20 log (V

3

/10

؋

V

)

IN

138

136

134

132

130

128

126

124

122

120

OUT

R1

+13V

20k⍀

R2

U1

V+

V–

V+

+

6

7

V

2k⍀

IN

20V p-p

2

V–

5

0

2k⍀

–

R4

U2

0

–13V

0

Figure 1. Channel Separation Test Circuit

FUNCTIONAL DESCRIPTION

The AD8610/AD8620 is manufactured on Analog Devices, Inc.’s

proprietary XFCB (eXtra Fast Complementary Bipolar) process.

XFCB is fully dielectrically isolated (DI) and used in conjunc-

tion with N-channel JFET technology and trimmable thin-film

resistors to create the world’s most precise JFET input amplifier.

Dielectrically isolated NPN and PNP transistors fabricated on

XFCB have F_Tgreater than 3 GHz. Low T_Cthin film resistors

enable very accurate offset voltage and offset voltage tempco

trimming. These process breakthroughs allowed Analog Devices’

world class IC designers to create an amplifier with faster slew

rate and more than 50% higher bandwidth at half of the current

consumed by its closest competition. The AD8610 is uncondi-

tionally stable in all gains, even with capacitive loads well in

excess of 1 nF. The AD8610B achieves less than 100 µV of offset

and 1 µV/°C of offset drift, numbers usually associated with very

high precision bipolar input amplifiers. The AD8610 is offered in

the tiny 8-lead MSOP as well as narrow 8-lead SOIC surface-

mount packages and is fully specified with supply voltages from

5 V to 13 V. The very wide specified temperature range, up to

125°C, guarantees superior operation in systems with little or no

active cooling.

50

100

300

0

150

200

250

350

FREQUENCY – kHz

Figure 2. AD8620 Channel Separation Graph

Power Consumption

A major advantage of the AD8610/AD8620 in new designs is

the saving of power. Lower power consumption of the AD8610

makes it much more attractive for portable instrumentation and

for high-density systems, simplifying thermal management, and

reducing power supply performance requirements. Compare the

power consumption of the AD8610/AD8620 versus the OPA627

in Figure 3.

8

7

OPA627

6

5

4

The unique input architecture of the AD8610 features extremely

low input bias currents and very low input offset voltage. Low

power consumption minimizes the die temperature and maintains

the very low input bias current. Unlike many competitive JFET

amplifiers, the AD8610/AD8620 input bias currents are low even

at elevated temperatures. Typical bias currents are less than 200 pA

at 85°C. The gate current of a JFET doubles every 10°C resulting

in a similar increase in input bias current over temperature.

Special care should be given to the PC board layout to minimize

leakage currents between PCB traces. Improper layout and

board handling generates leakage current that exceeds the bias

current of the AD8610/AD8620.

3

AD8610

2

–75

–50

–25

0

25

50

75

100

125

TEMPERATURE – ؇C

Figure 3. Supply Current vs. Temperature

REV. D

–9–

AD8610/AD8620

Driving Large Capacitive Loads

The AD8610 has excellent capacitive load driving capability and

can safely drive up to 10 nF when operating with 5 V supply.

Figures 4 and 5 compare the AD8610/AD8620 against the OPA627

in the noninverting gain configuration driving a 10 kΩ resistor and

10,000 pF capacitor placed in parallel on its output, with a square

wave input set to a frequency of 200 kHz. The AD8610 has much

less ringing than the OPA627 with heavy capacitive loads.

+5V

7

3

2

V

IN

= 50mV

4

2␮F

–5V

2k⍀

Figure 6. Capacitive Load Drive Test Circuit

V

R

C

= ؎5V

= 10k⍀

= 10,000pF

S

L

V

R

C

= ؎5V

= 10k⍀

= 2␮F

S

L

TIME – 2␮s/DIV

TIME – 20␮s/DIV

Figure 4. OPA627 Driving C_L= 10,000 pF

Figure 7. OPA627 Capacitive Load Drive, A_V= +2

V

R

C

= ؎5V

S

L

V

R

C

= ؎5V

= 10k⍀

= 2␮F

S

= 10k⍀

= 10,000pF

L

TIME – 2␮s/DIV

TIME – 20␮s/DIV

Figure 5. AD8610/AD8620 Driving C_L= 10,000 pF

Figure 8. AD8610/AD8620 Capacitive Load Drive, A_V= +2

The AD8610/AD8620 can drive much larger capacitances without

any external compensation. Although the AD8610/AD8620 is stable

with very large capacitive loads, remember that this capacitive

loading will limit the bandwidth of the amplifier. Heavy capacitive

loads will also increase the amount of overshoot and ringing at the

output. Figures 7 and 8 show the AD8610/AD8620 and the OPA627

in a noninverting gain of +2 driving 2 µF of capacitance load. The

ringing on the OPA627 is much larger in magnitude and continues

more than 10 times longer than the AD8610.

Slew Rate (Unity Gain Inverting vs. Noninverting)

Amplifiers generally have a faster slew rate in an inverting unity

gain configuration due to the absence of the differential input

capacitance. Figures 9 through 12 show the performance of the

AD8610 configured in a gain of –1 compared to the OPA627.

The AD8610 slew rate is more symmetrical, and both the positive

and negative transitions are much cleaner than in the OPA627.

–10–

REV. D

AD8610/AD8620

V

R

= ؎13V

= 2k⍀

V

R

= ؎13V

= 2k⍀

S

L

G = –1

SR = 56V/␮s

SR = 54V/␮s

TIME – 400ns/DIV

Figure 12. (–SR) of OPA627 in Unity Gain of –1

Figure 9. (+SR) of AD8610/AD8620 in Unity Gain of –1

The AD8610 has a very fast slew rate of 60 V/µs even when config-

ured in a noninverting gain of +1. This is the toughest condition to

impose on any amplifier since the input common-mode capacitance

of the amplifier generally makes its SR appear worse. The slew

rate of an amplifier varies according to the voltage difference

between its two inputs. To observe the maximum SR as specified

in the AD8610 data sheet, a difference voltage of about 2 V between

the inputs must be ensured. This will be required for virtually any

JFET op amp so that one side of the op amp input circuit is com-

pletely off, maximizing the current available to charge and discharge

the internal compensation capacitance. Lower differential

drive voltages will produce lower slew rate readings. A JFET-

input op amp with a slew rate of 60 V/µs at unity gain with

V_IN= 10 V might slew at 20 V/µs if it is operated at a gain of

+100 with V_IN= 100 mV.

V

R

= ؎13V

= 2k⍀

S

L

G = –1

SR = 42.1V/␮s

TIME – 400ns/DIV

The slew rate of the AD8610/AD8620 is double that of the OPA627

when configured in a unity gain of +1 (see Figures 13 and 14).

Figure 10. (+SR) of OPA627 in Unity Gain of –1

V

R

= ؎13V

= 2k⍀

S

V

R

= ؎13V

= 2k⍀

L

S

G = –1

L

G = +1

SR = 54V/␮s

SR = 85V/␮s

TIME – 400ns/DIV

Figure 11. (–SR) of AD8610/AD8620 in Unity Gain of –1

Figure 13. (+SR) of AD8610/AD8620 in Unity Gain of +1

REV. D

–11–

AD8610/AD8620

diodes greatly interfere with many application circuits such as

precision rectifiers and comparators. The AD8610 is free from

these limitations.

V

R

= ؎13V

= 2k⍀

S

L

G = +1

+13V

3

7

6

V1

2

SR = 23V/␮s

4

AD8610

14V

–13V

0

Figure 16. Unity Gain Follower

No Phase Reversal

Many amplifiers misbehave when one or both of the inputs are

forced beyond the input common-mode voltage range. Phase

reversal is typified by the transfer function of the amplifier,

effectively reversing its transfer polarity. In some cases, this can

cause lockup and even equipment damage in servo systems, and

may cause permanent damage or nonrecoverable parameter

shifts to the amplifier itself. Many amplifiers feature compensation

circuitry to combat these effects, but some are only effective for

the inverting input. The AD8610/AD8620 is designed to prevent

phase reversal when one or both inputs are forced beyond their

input common-mode voltage range.

TIME – 400ns/DIV

Figure 14. (+SR) of OPA627 in Unity Gain of +1

The slew rate of an amplifier determines the maximum frequency

at which it can respond to a large signal input. This frequency

(known as full-power bandwidth, or FPBW) can be calculated

from the equation:

SR

FPBW =

2π ×V

(

)

PEAK

for a given distortion (e.g., 1%).

V

IN

CH = 20.8V

1

p-p

0V

CH = 19.4V

2

p-p

V

OUT

0V

0

TIME – 400␮s/DIV

Figure 17. No Phase Reversal

THD Readings vs. Common-Mode Voltage

Total harmonic distortion of the AD8610/AD8620 is well below

0.0006% with any load down to 600 Ω. The AD8610/AD8620

outperforms the OPA627 for distortion, especially at frequen-

cies above 20 kHz.

TIME – 400ns/DIV

Figure 15. AD8610 FPBW

Input Overvoltage Protection

When the input of an amplifier is driven below V_EEor above V_CC

by more than one V_BE, large currents will flow from the substrate

through the negative supply (V–) or the positive supply (V+),

respectively, to the input pins, which can destroy the device. If the

input source can deliver larger currents than the maximum forward

current of the diode (>5 mA), a series resistor can be added to

protect the inputs. With its very low input bias and offset current, a

large series resistor can be placed in front of the AD8610 inputs to

limit current to below damaging levels. Series resistance of 10 kΩ

will generate less than 25 µV of offset. This 10 kΩ will allow input

voltages more than 5 V beyond either power supply. Thermal noise

generated by the resistor will add 7.5 nV/√Hz to the noise of the

AD8610. For the AD8610/AD8620, differential voltages equal to

the supply voltage will not cause any problem (see Figure 15).

In this context, it should also be noted that the high breakdown

voltage of the input FETs eliminates the need to include clamp

diodes between the inputs of the amplifier, a practice that is

mandatory on many precision op amps. Unfortunately, clamp

0.1

V

= ؎13V

= 5V rms

SY

V

IN

BW = 80kHz

0.01

OPA627

AD8610

0.001

0.0001

10

100

1k

10k

80k

FREQUENCY – Hz

Figure 18. AD8610 vs. OPA627 THD + Noise @ V_CM= 0 V

REV. D

–12–

AD8610/AD8620

0.1

1.2k

1.0k

800

600

400

200

0

V

R

= ؎13V

= 600⍀

SY

L

2V rms

0.01

4V rms

6V rms

OPA627

0.001

10

100

1k

FREQUENCY – Hz

10k 20k

0.001

0.01

0.1

1

10

ERROR BAND – %

Figure 21. OPA627 Settling Time vs. Error Band

Figure 19. THD + Noise vs. Frequency

The AD8610/AD8620 maintains this fast settling when loaded

with large capacitive loads as shown in Figure 22.

Noise vs. Common-Mode Voltage

AD8610 noise density varies only 10% over the input range as

shown in Table I.

3.0

ERROR BAND ؎0.01%

Table I. Noise vs. Common-Mode Voltage

2.5

2.0

1.5

1.0

0.5

0.0

V_CMat F = 1 kHz (V)

Noise Reading (nV/√Hz)

–10

–5

0

+5

+10

7.21

6.89

6.73

6.41

7.21

Settling Time

The AD8610 has a very fast settling time, even to a very tight error

band, as can be seen from Figure 20. The AD8610 is configured

in an inverting gain of +1 with 2 kΩ input and feedback resistors.

The output is monitored with a 10 ×, 10 M, 11.2 pF scope probe.

0

500

1000

– pF

1500

2000

C

L

Figure 22. AD8610 Settling Time vs. Load Capacitance

1.2k

1.0k

800

600

400

3.0

ERROR BAND ؎0.01%

2.5

2.0

1.5

1.0

0.5

0.0

200

0

0.01

0.1

1

10

0.001

ERROR BAND – %

0

500

1000

– pF

1500

2000

Figure 20. AD8610 Settling Time vs. Error Band

C

L

Figure 23. OPA627 Settling Time vs. Load Capacitance

Output Current Capability

The AD8610 can drive very heavy loads due to its high output

current. It is capable of sourcing or sinking 45 mA at 10 V output.

The short circuit current is quite high and the part is capable of

sinking about 95 mA and sourcing over 60 mA while operating with

REV. D

–13–

AD8610/AD8620

supplies of 5 V. Figures 24 and 25 compare the load current

versus output voltage of AD8610/AD8620 and OPA627.

Programmable Gain Amplifier (PGA)

The combination of low noise, low input bias current, low input

offset voltage, and low temperature drift make the AD8610 a

perfect solution for programmable gain amplifiers. PGAs are often

used immediately after sensors to increase the dynamic range of

the measurement circuit. Historically, the large ON resistance of

switches, combined with the large I_Bcurrents of amplifiers,

created a large dc offset in PGAs. Recent and improved monolithic

switches and amplifiers completely remove these problems. A PGA

discrete circuit is shown in Figure 27. In Figure 27, when the 10 pA

bias current of the AD8610 is dropped across the (<5 Ω) R_ONof

the switch, it results in a negligible offset error.

10

1

V

EE

V

CC

When high precision resistors are used, as in the circuit of Figure 27,

the error introduced by the PGA is within the 1/2 LSB requirement

for a 16-bit system.

0.1

0.00001

+5V

0.0001

0.001

0.01

0.1

1

LOAD CURRENT – A

Figure 24. AD8610 Dropout from 13 V vs. Load Current

V

IN

100⍀

10

AD8610

V

OUT

U10

5

10k⍀

V

CC

5pF

–5V

V

EE

+5V +5V

1

12

13

V

L

V

DD

1k⍀

S1

D1

3

2

G = 1

1

16

9

IN1

IN2

IN3

IN4

10k⍀

ADG452

S2 14

G

Y0

Y1

Y2

Y3

G = 10

0.1

0.00001

1k⍀

100⍀

11⍀

D2 15

S3 11

A

B

0.0001

0.001

LOAD CURRENT – A

0.01

0.1

1

A0

A1

74HC139

G = 100

Figure 25. OPA627 Dropout from 15 V vs. Load Current

D3 10

Although operating conditions imposed on the AD8610 ( 13 V)

are less favorable than the OPA627 ( 15 V), it can be seen that the

AD8610 has much better drive capability (lower headroom to the

supply) for a given load current.

S4

6

8

G = 1000

D4

7

V

SS

GND

5

4

Operating with Supplies Greater than 13 V

–5V

The AD8610 maximum operating voltage is specified at 13 V.

When 13 V is not readily available, an inexpensive LDO can

provide 12 V from a nominal 15 V supply.

Figure 27. High Precision PGA

1. Room temperature error calculation due to R_ONand I_B:

Input Offset Voltage Adjustment

∆V_OS= I_B× R_ON= 2pA× 5 Ω = 10pV

Total Offset = AD8610(Offset) + ∆V_OS

Total Offset = AD8610(Offset _Trimmed) + ∆V_OS

Total Offset = 5 µV+10pV ≅ 5 µV

Offset of AD8610 is very small and normally does not require

additional offset adjustment. However, the offset adjust pins can

be used as shown in Figure 26 to further reduce the dc offset. By

using resistors in the range of 50 kΩ, offset trim range is 3.3 mV.

+V

S

2. Full temperature error calculation due to R_ONand I_B:

7

2

3

∆V_OS

(

@

85°C) = I_B(

@

85°C) × R_ON

(@ 85°C) =

6

V

OUT

AD8610

250 pA × 15 Ω = 3.75 nV

1

3. Temperature coefficient of switch and AD8610/AD8620

combined is essentially the same as the T_CV_OSof the AD8610:

5

R1

4

∆V_OS/∆T(total) = ∆V_OS/∆T(AD8610) + ∆V_OS/∆T(I_B× R_ON

∆V_OS/∆T(total) = 0.5 µ V/ °C+ 0.06 nV/ °C ≅ 0.5 µ V/ °C

)

–V

S

Figure 26. Offset Voltage Nulling Circuit

–14–

REV. D

AD8610/AD8620

In active filter applications using operational amplifiers, the

dc accuracy of the amplifier is critical to optimal filter performance.

The amplifier’s offset voltage and bias current contribute to output

error. Input offset voltage is passed by the filter, and may be

amplified to produce excessive output offset. For low frequency

applications requiring large value input resistors, bias and offset

currents flowing through these resistors will also generate an

offset voltage.

High Speed Instrumentation Amplifier (IN AMP)

The three op amp instrumentation amplifiers shown in Figure 28

can provide a range of gains from unity up to 1,000 or higher. The

instrumentation amplifier configuration features high common-

mode rejection, balanced differential inputs, and stable, accurately

defined gain. Low input bias currents and fast settling are achieved

with the JFET input AD8610/AD8620. Most instrumentation

amplifiers cannot match the high frequency performance of this

circuit. The circuit bandwidth is 25 MHz at a gain of 1, and close

to 5 MHz at a gain of 10. Settling time for the entire circuit is

550 ns to 0.01% for a 10 V step (gain = 10). Note that the resistors

around the input pins need to be small enough in value so that

the RC time constant they form in combination with stray circuit

capacitance does not reduce circuit bandwidth.

At higher frequencies, an amplifier’s dynamic response must be

carefully considered. In this case, slew rate, bandwidth, and open-

loop gain play a major role in amplifier selection. The slew rate

must be both fast and symmetrical to minimize distortion. The

amplifier’s bandwidth, in conjunction with the filter’s gain, will

dictate the frequency response of the filter. The use of a high perfor-

mance amplifier such as the AD8610/AD8620 will minimize both

dc and ac errors in all active filter applications.

V+

V

IN1

Second-Order Low-Pass Filter

Figure 29 shows the AD8610 configured as a second-order

Butterworth low-pass filter. With the values as shown, the corner

frequency of the filter will be 1 MHz. The wide bandwidth of

the AD8610/AD8620 allows a corner frequency up to tens of

megaHertz. The following equations can be used for component

selection:

1/2 AD8620

U1

V–

C5

10pF

V+

R1 = R2 = User Selected Typical Values:10 kΩ −100 kΩ

(

)

R1 1k⍀

1.414

C1 =

C2 =

V

OUT

R4 2k⍀

2π f

R1

(

)( _CUTOFF)(

)

C4

15pF

R7

2k⍀

AD8610

U2

0.707

R6

2k⍀

2π

f

R1

(

)( _CUTOFF)(

)

RG

V–

R8 2k⍀

where C1 and C2 are in farads.

R5 2k⍀

C1

22pF

C3

15pF

V

IN2

1/2 AD8620

+13V

U

1

V

IN

R2 1k⍀

5

V

OUT

R2

10k⍀

R1

10k⍀

AD8610

C2

10pF

U1

C2

11pF

Figure 28. High Speed Instrumentation Amplifier

High Speed Filters

–13V

The four most popular configurations are Butterworth, Elliptical,

Bessel, and Chebyshev. Each type has a response that is optimized

for a given characteristic as shown in Table II.

Figure 29. Second-Order Low-Pass Filter

Table II. Filter Types

Type

Sensitivity

Overshoot

Phase

Nonlinear

Linear

Amplitude (Pass Band)

Butterworth

Chebyshev

Elliptical

Moderate

Good

Best

Good

Moderate

Poor

Max Flat

Equal Ripple

Bessel (Thompson)

Poor

Best

REV. D

–15–

AD8610/AD8620

High Speed, Low Noise Differential Driver

U2

3

2

The AD8620 is a perfect candidate as a low noise differential

driver for many popular ADCs. There are also other applications,

such as balanced lines, that require differential drivers. The circuit

of Figure 30 is a unique line driver widely used in industrial applica-

tions. With 13 V supplies, the line driver can deliver a differential

signal of 23 V p-p into a 1 kΩ load. The high slew rate and wide

bandwidth of the AD8620 combine to yield a full power bandwidth

of 145 kHz while the low noise front end produces a referred-to-

input noise voltage spectral density of 6 nV/√Hz. The design is a

transformerless, balanced transmission system where output

common-mode rejection of noise is of paramount importance.

Like the transformer-based design, either output can be shorted

to ground for unbalanced line driver applications without changing

the circuit gain of 1. This allows the design to be easily set to

noninverting, inverting, or differential operation.

V+

V–

V

1

O

1

R4 1k⍀

R5

R10

1k⍀

50⍀

R8 1k⍀

R13

1k⍀

1/2 OF AD8620

3

2

V+

V–

6

R6

10k⍀

R1

1k⍀

R12

1k⍀

AD8610

0

R7

1k⍀

R9 1k⍀

5

V+

7

R3 1k⍀

1/2 OF AD8620

R2

R11

50⍀

V

2

O

V–

6

U3

1k⍀

V

2 – V 1 =V

O

IN

0

Figure 30. Differential Driver

–16–

REV. D

AD8610/AD8620

OUTLINE DIMENSIONS

8-Lead Mini Small Outline Package [MSOP]

(RM-8)

8-Lead Standard Small Outline Package [SOIC]

Narrow Body

(R-8)

Dimensions shown in millimeters

Dimensions shown in millimeters and (inches)

3.00

BSC

5.00 (0.1968)

4.80 (0.1890)

8

5

4

8

1

5

4

4.90

BSC

3.00

BSC

6.20 (0.2440)

5.80 (0.2284)

4.00 (0.1574)

3.80 (0.1497)

1

PIN 1

0.50 (0.0196)

0.25 (0.0099)

1.27 (0.0500)

BSC

0.65 BSC

؋

45؇

1.75 (0.0688)

1.35 (0.0532)

0.25 (0.0098)

0.10 (0.0040)

1.10 MAX

0.15

0.00

8؇

0.80

0.60

0.40

0.51 (0.0201)

0.31 (0.0122)

0؇ 1.27 (0.0500)

8؇

0؇

COPLANARITY

0.10

0.25 (0.0098)

0.17 (0.0067)

0.38

0.22

0.23

0.08

SEATING

PLANE

0.40 (0.0157)

SEATING

PLANE

COPLANARITY

0.10

COMPLIANT TO JEDEC STANDARDS MS-012AA

CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS

(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR

REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN

COMPLIANT TO JEDEC STANDARDS MO-187AA

REV. D

–17–

AD8610/AD8620

Revision History

Location

Page

2/04—Data Sheet changed from REV. C to REV. D.

Changes to SPECIFICATIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2

Changes to ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4

Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17

10/02—Data Sheet changed from REV. B to REV. C.

Updated ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4

Edits to Figure 15 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12

Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16

5/02—Data Sheet changed from REV. A to REV. B.

Addition of part number AD8620 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .Universal

Addition of 8-Lead SOIC (R-8 Suffix) Drawing . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1

Changes to GENERAL DESCRIPTION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1

Additions to SPECIFICATIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2

Change to ELECTRICAL SPECIFICATIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3

Additions to ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4

Replace TPC 29 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8

Add Channel Separation Test Circuit Figure . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9

Add Channel Separation Graph . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9

Changes to Figure 26 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15

Addition of High-Speed, Low Noise Differential Driver section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16

Addition of Figure 30 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16

–18–

REV. D

–19–

–20–

型号:	AD8610ARZ
Brand Name：	Analog Devices Inc
是否无铅：	含铅
是否Rohs认证：	符合
生命周期：	Active
零件包装代码：	SOIC
包装说明：	SOP, SOP8,.25
针数：	8
制造商包装代码：	R-8
Reach Compliance Code：	compliant
ECCN代码：	EAR99
HTS代码：	8542.31.00.01
风险等级：	0.91
放大器类型：	OPERATIONAL AMPLIFIER
架构：	VOLTAGE-FEEDBACK
最大平均偏置电流 (IIB)：	0.0025 µA
25C 时的最大偏置电流 (IIB)：	0.00001 µA
标称共模抑制比：	95 dB
频率补偿：	YES
最大输入失调电压：	850 µV
JESD-30 代码：	R-PDSO-G8
JESD-609代码：	e3
长度：	4.9 mm
低-偏置：	YES
低-失调：	YES
湿度敏感等级：	1
负供电电压上限：	-13.65 V
标称负供电电压 (Vsup)：	-5 V
功能数量：	1
端子数量：	8
最高工作温度：	125 °C
最低工作温度：	-40 °C
封装主体材料：	PLASTIC/EPOXY
封装代码：	SOP
封装等效代码：	SOP8,.25
封装形状：	RECTANGULAR
封装形式：	SMALL OUTLINE
峰值回流温度（摄氏度）：	260
电源：	+-5/+-13 V
认证状态：	Not Qualified
座面最大高度：	1.75 mm
最小摆率：	40 V/us
标称压摆率：	50 V/us
子类别：	Operational Amplifier
最大压摆率：	4 mA
供电电压上限：	13.65 V
标称供电电压 (Vsup)：	5 V
表面贴装：	YES
技术：	BIPOLAR
温度等级：	AUTOMOTIVE
端子面层：	Matte Tin (Sn)
端子形式：	GULL WING
端子节距：	1.27 mm
端子位置：	DUAL
处于峰值回流温度下的最长时间：	30
标称均一增益带宽：	25000 kHz
最小电压增益：	100000
宽度：	3.9 mm
Base Number Matches：	1

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