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HCNR200 and HCNR201

High-Linearity Analog Optocouplers

Data Sheet

Lead (Pb) Free

RoHS 6 fully

compliant

RoHS 6 fully compliant options available;

-xxxE denotes a lead-free product

Description

Features

 Low nonlinearity: 0.01%

 K₃(I_PD2/I_PD1) transfer gain

HCNR200: 1ꢀ%

HCNR201: ꢀ%

 Low gain temperature coeﬃcient: -6ꢀppm/°C

 Wide bandwidth – DC to >1 MHz

 Worldwide safety approval

– UL 1ꢀ77 recognized (ꢀ kV rms/1 min rating)

– CSA approved

The HCNR200/201 high-linearity analog optocoupler

consists of a high-performance AlGaAs LED that illumi-

nates two closely matched photodiodes. The input pho-

todiode can be used to monitor, and therefore stabilize,

the light output of the LED. As a result, the non-linearity

and drift characteristics of the LED can be virtually elimi-

nated. The output photodiode produces a photocurrent

that is linearly related to the light output of the LED. The

close matching of the photo-diodes and advanced de-

sign of the package ensure the high linearity and stable

gain characteristics of the optocoupler.

– IEC/EN/DIN EN 60747-ꢀ-2 approved

V_IORM= 1414 V _peak(option #0ꢀ0)

The HCNR200/201 can be used to isolate analog signals

in a wide variety of applications that require good stabil-

ity, linearity, bandwidth and low cost. The HCNR200/201

is very ﬂexible and, by appropriate design of the appli-

cation circuit, is capable of operating in many diﬀerent

modes, including: unipolar/bipolar, ac/dc and inverting/

non-inverting. The HCNR200/201 is an excellent solution

for many analog isolation problems.

 Surface mount option available (Option #300)

 8-Pin DIP package - 0.400”spacing

 Allows ﬂexible circuit design

Applications

 Low cost analog isolation

 Telecom: Modem, PBX

 Industrial process control:

Transducer isolator

Schematic

Isolator for thermocouples 4mA to 20 mA loop isola-

tion

 SMPS feedback loop, SMPS feedforward

 Monitor motor supply voltage

 Medical

1

8

LED CATHODE

NC

-

V

F

I

+

F

LED ANODE

2

3

7

6

PD1 CATHODE

PD1 ANODE

PD2 CATHODE

PD2 ANODE

I

PD2

PD1

4

5

CAUTION: It is advised that normal static precautions be taken in handling and assembly

of this component to prevent damage and/or degradation which may be induced by ESD.

Ordering Information

HCNR200/HCNR201 is UL Recognized with ꢀ000 Vrms for 1 minute per UL1ꢀ77.

Option

IEC/EN/DIN EN

Part

Number

RoHS

non RoHS

Surface Gull

Tape

UL 5000 Vrms/ 60747-5-2

1 Minute rating V_IORM= 1414 V_peak

Compliant Compliant Package

Mount

Wing & Reel

Quantity

-000E

-300E

no option 400 mil

X

42 per tube

7ꢀ0 per reel

42 per tube

7ꢀ0 per reel

#300

#ꢀ00

#0ꢀ0

#3ꢀ0

#ꢀꢀ0

Widebody

DIP-8

X

HCNR200 -ꢀ00E

HCNR201 -0ꢀ0E

-3ꢀ0E

X

-ꢀꢀ0E

X

To order, choose a part number from the part number column and combine with the desired option from the option

column to form an order entry.

Example 1:

HCNR200-ꢀꢀ0E to order product of Gull Wing Surface Mount package in Tape and Reel packaging with IEC/EN/

DIN EN 60747-ꢀ-2 V_IORM= 1414 V_peakSafety Approval and UL ꢀ000 Vrms for 1 minute rating and RoHS compliant.

Example 2:

HCNR201 to order product of 8-Pin Widebody DIP package in Tube packaging with UL ꢀ000 Vrms for 1 minute rating

and non RoHS compliant.

Option datasheets are available. Contact your Avago sales representative or authorized distributor for information.

Remarks: The notation ‘#XXX’is used for existing products, while (new) products launched since July 1ꢀ, 2001 and

RoHS compliant will use ‘–XXXE.’

2

Package Outline Drawings

0.20 (0.008)

0.30 (0.012)

11.30 (0.445)

MAX.

8

7

6

5

MARKING

9.00

(0.354)

TYP.

A

10.16

(0.400)

TYP.

HCNR200

XXX

yyww

11.00

(0.433)

MAX.

z

0°

15°

*

2

3

4

1

ONE

1.50

(0.059)

MAX.

1

2

8

7

NC

5.10 (0.201) MAX.

LED

K

2

1

0.51 (0.021) MIN.

3

4

6

5

3.10 (0.122)

3.90 (0.154)

PD1

PD2

1.70 (0.067)

1.80 (0.071)

0.40 (0.016)

0.56 (0.022)

DIMENSIONS IN MILLIMETERS AND (INCHES).

MARKING :

2.54 (0.100) TYP.

XXX = 050 ONLY if option #050,#350,#550 (or -050,-350,-550)

ordered (otherwise blank)

yy

- Year

ww

- Work Week

Marked with black dot - Designates Lead Free option E

*

- Designates pin 1

NOTE: FLOATING LEAD PROTRUSION IS 0.25 mm (10 mils) MAX.

Figure 1a. 8 PIN DIP

3

Gull Wing Surface Mount Option #300

11.15 0.15

(0.442 0.006)

LAND PATTERN RECOMMENDATION

6

7

5

8

9.00 0.15

(0.354 0.006)

13.56

(0.534)

1

3

2

4

2.29

(0.09)

1.3

(0.051)

12.30 0.30

1.55

(0.061)

MAX.

(0.484 0.012)

11.00

MAX.

(0.433)

4.00

(0.158)

MAX.

1.78 0.15

(0.070 0.006)

1.00 0.15

(0.039 0.006)

0.75 0.25

(0.030 0.010)

+ 0.076

- 0.0051

2.54

(0.100)

BSC

0.254

+ 0.003)

- 0.002)

(0.010

DIMENSIONS IN MILLIMETERS (INCHES).

7° NOM.

LEAD COPLANARITY = 0.10 mm (0.004 INCHES).

NOTE: FLOATING LEAD PROTRUSION IS 0.25 mm (10 mils) MAX.

Figure 1b. 8 PIN Gull Wing Surface Mount Option #300

4

Solder Reﬂow Temperature Proﬁle

300

PREHEATING RATE 3 °C + 1 °C/–0.5 °C/SEC.

REFLOW HEATING RATE 2.5 °C 0.5 °C/SEC.

PEAK

TEMP.

245 °C

PEAK

TEMP.

240 °C

PEAK

TEMP.

230 °C

200

100

0

2.5 C 0.5 °C/SEC.

SOLDERING

30

TIME

160 °C

150 °C

140 °C

SEC.

200 °C

30

SEC.

3 °C + 1 °C/–0.5 °C

PREHEATING TIME

150 °C, 90 + 30 SEC.

50 SEC.

TIGHT

TYPICAL

LOOSE

ROOM

TEMPERATURE

0

50

100

150

200

250

TIME (SECONDS)

NOTE: NON-HALIDE FLUX SHOULD BE USED.

Recommended Pb-Free IR Proﬁle

TIME WITHIN 5 °C of ACTUAL PEAK TEMPERATURE

t_p

15 SEC.

* 245 +0/-5 °C

RAMP-UP

T_p

217 °C

T_L

RAMP-DOWN

6 °C/SEC. MAX.

3 °C/SEC. MAX.

150 - 200 °C

T_smax

T_smin

NOTES:

t_s

THE TIME FROM 25 °C to PEAK

TEMPERATURE = 8 MINUTES MAX.

_smax= 200 °C, T_smin= 150 °C

t_L

PREHEAT

60 to 180 SEC.

60 to 150 SEC.

T

NOTE: NON-HALIDE FLUX SHOULD BE USED.

25

t 25 °C to PEAK

TIME

Regulatory Information

The HCNR200/201 optocoupler features a 0.400”wide, eight pin DIP package. This package was speciﬁcally designed

to meet worldwide regulatory requirements. The HCNR200/201 has been approved by the following organizations:

IEC/EN/DIN EN 60747-5-2

UL

Approved under

Recognized under UL 1ꢀ77, Component Recognition

Program, FILE Eꢀꢀ361

IEC 60747-ꢀ-2:1997 + A1:2002

EN 60747-ꢀ-2:2001 + A1:2002

DIN EN 60747-ꢀ-2 (VDE 0884 Teil 2):2003-01

(Option 0ꢀ0 only)

CSA

Approved under CSA Component Acceptance Notice

#ꢀ, File CA 88324

ꢀ

Insulation and Safety Related Speciﬁcations

Parameter

Symbol

Value

Units

Conditions

Min. External Clearance

(External Air Gap)

L(IO1)

9.6

mm

Measured from input terminals to output

terminals, shortest distance through air

Min. External Creepage

(External Tracking Path)

L(IO2)

10.0

1.0

mm

Measured from input terminals to output

terminals, shortest distance path along body

Min. Internal Clearance

(Internal Plastic Gap)

Through insulation distance conductor to

conductor, usually the direct distance

between the photoemitter and photodetector

inside the optocoupler cavity

Min. Internal Creepage

(Internal Tracking Path)

4.0

mm

V

The shortest distance around the border

between two diﬀerent insulating materials

measured between the emitter and detector

Comparative Tracking Index

Isolation Group

CTI

200

IIIa

DIN IEC 112/VDE 0303 PART 1

Material group (DIN VDE 0110)

Option 300 – surface mount classiﬁcation is Class A in accordance with CECC 00802.

IEC/EN/DIN EN 60747-5-2 Insulation Characteristics (Option #050 Only)

Description

Symbol

Characteristic

Unit

Installation classiﬁcation per DIN VDE 0110/1.89, Table 1

For rated mains voltage ≤600 V rms

For rated mains voltage ≤1000 V rms

I-IV

I-III

Climatic Classiﬁcation (DIN IEC 68 part 1)

Pollution Degree (DIN VDE 0110 Part 1/1.89)

Maximum Working Insulation Voltage

ꢀꢀ/100/21

2

V

1414

26ꢀ1

V _peak

IORM

Input to Output Test Voltage, Method b*

V_PR

V_PR= 1.87ꢀ x V_IORM, 100% Production Test with

t_m= 1 sec, Partial Discharge < ꢀ pC

Input to Output Test Voltage, Method a*

V_PR= 1.ꢀ x V_IORM, Type and sample test, t_m= 60 sec,

Partial Discharge < ꢀ pC

V_PR

2121

8000

V _peak

Highest Allowable Overvoltage*

V_IOTM

V _peak

(Transient Overvoltage, t_ini= 10 sec)

Safety-Limiting Values

(Maximum values allowed in the event of a failure,

also see Figure 11)

Case Temperature

Current (Input Current I_F, P_S= 0)

Output Power

T_S

I_S

P_S,OUTPUT

1ꢀ0

400

700

°C

mA

mW

Insulation Resistance at T_S, V_IO= ꢀ00 V

R_S

>10⁹

Ω

*Refer to the front of the Optocoupler section of the current catalog for a more detailed description of IEC/EN/DIN EN 60747-ꢀ-2 and other prod-

uct safety regulations.

Note: Optocouplers providing safe electrical separation per IEC/EN/DIN EN 60747-ꢀ-2 do so only within the safety-limiting values to which they

are qualiﬁed. Protective cut-out switches must be used to ensure that the safety limits are not exceeded.

6

Absolute Maximum Ratings

Storage Temperature ..............................................................................................-ꢀꢀ°C to +12ꢀ°C

Operating Temperature (T )................................................................................. -ꢀꢀ°C to +100°C

A

Junction Temperature (T_J) ......................................................................................................... 12ꢀ°C

Reﬂow Temperature Proﬁle ..............................................See Package Outline Drawings Section

Lead Solder Temperature ............................................................................................260°C for 10s

(up to seating plane)

Average Input Current - I_F........................................................................................................ 2ꢀ mA

Peak Input Current - I_F............................................................................................................... 40 mA

(ꢀ0 ns maximum pulse width)

Reverse Input Voltage - V_R............................................................................................................2.ꢀ V

(I_R= 100 μA, Pin 1-2)

Input Power Dissipation....................................................................................60 mW @ T = 8ꢀ°C

A

(Derate at 2.2 mW/°C for operating temperatures above 8ꢀ°C)

Reverse Output Photodiode Voltage ........................................................................................30 V

(Pin 6-ꢀ)

Reverse Input Photodiode Voltage............................................................................................30 V

(Pin 3-4)

Recommended Operating Conditions

Storage Temperature .................................................................................................-40°C to +8ꢀ°C

Operating Temperature ............................................................................................-40°C to +8ꢀ°C

Average Input Current - I_F.................................................................................................. 1 - 20 mA

Peak Input Current - I_F............................................................................................................... 3ꢀ mA

(ꢀ0% duty cycle, 1 ms pulse width)

Reverse Output Photodiode Voltage ..................................................................................0 - 1ꢀ V

(Pin 6-ꢀ)

Reverse Input Photodiode Voltage......................................................................................0 - 1ꢀ V

(Pin 3-4)

7

Electrical Speciﬁcations

T = 2ꢀ°C unless otherwise speciﬁed.

A

Parameter

Symbol

Device

Min.

Typ.

Max.

Units

Test Conditions

Fig.

Note

Transfer Gain

K₃

HCNR200

0.8ꢀ

1.00

1.1ꢀ

ꢀ nA < I_PD< ꢀ0 μA,

0 V < V_PD< 1ꢀ V

2,3

1

HCNR201

0.9ꢀ

0.93

1.00

1.0ꢀ

1.07

ꢀ nA < I_PD< ꢀ0 μA,

0 V < V_PD< 1ꢀ V

1

-40°C < T < 8ꢀ°C,

A

ꢀ nA < I_PD< ꢀ0 μA,

0 V < V_PD< 1ꢀ V

Temperature

Coeﬃcient of

Transfer Gain

ΔK₃/ΔT

-6ꢀ

ppm/°C -40°C < T < 8ꢀ°C,

2,3

A

ꢀ nA < I_PD< ꢀ0 μA,

0 V < V_PD< 1ꢀ V

DC NonLinearity

(Best Fit)

NL_BF

HCNR200

HCNR201

0.01

0.2ꢀ

0.0ꢀ

0.07

%

ꢀ nA < I_PD< ꢀ0 μA,

0 V < V_PD< 1ꢀ V

4,ꢀ,

6

2

ꢀ nA < I_PD< ꢀ0 μA,

0 V < V_PD< 1ꢀ V

-40°C < T < 8ꢀ°C,

A

ꢀ nA < I_PD< ꢀ0 μA,

0 V < V_PD< 1ꢀ V

DC Nonlinearity

(Ends Fit)

NL_EF

K₁

0.016

ꢀ nA < I_PD< ꢀ0 μA,

0 V < V_PD< 1ꢀ V

3

%

Input Photo-

diode Current

Transfer Ratio

(I_PD1/I_F)

HCNR200

HCNR201

0.2ꢀ

0.36

0.ꢀ0

0.48

0.7ꢀ

0.72

I_F= 10 mA,

0 V < V_PD1< 1ꢀ V

7

Temperature

Coeﬃcient

of K₁

ΔK₁/ΔT

-0.3

%/°C

-40°C < T < 8ꢀ°C,

I_F= 10 mA

0 V < V_PD1< 1ꢀ V

7

8

A

Photodiode

Leakage Current

I_LK

0.ꢀ

2ꢀ

nA

V

I_F= 0 mA,

0 V < V_PD< 1ꢀ V

Photodiode

BV_RPD

30

1ꢀ0

I_R= 100 μA

Reverse Break-

down Voltage

Photodiode

Capacitance

C_PD

V_F

22

pF

V

V_PD= 0 V

LED Forward

Voltage

1.3

1.2

1.6

1.8ꢀ

1.9ꢀ

I_F= 10 mA

I_F= 10 mA,

9,

10

-40°C < T < 8ꢀ°C

A

LED Reverse

Breakdown

Voltage

BV_R

2.ꢀ

9

V

mV/°C

pF

I_F= 100 μA

I_F= 10 mA

f = 1 MHz,

Temperature

Coeﬃcient of

Forward Voltage

ΔV /ΔT

-1.7

80

F

A

LED Junction

Capacitance

C_LED

V = 0 V

F

8

AC Electrical Speciﬁcations

T = 2ꢀ°C unless otherwise speciﬁed.

A

Test

Conditions

Parameter

Symbol

Device

Min.

Typ. Max. Units

Fig. Note

LED Bandwidth

f -3dB

9

MHz

I_F= 10 mA

Application Circuit Bandwidth:

High Speed

High Precision

1.ꢀ

10

MHz

kHz

16

17

6

Application Circuit: IMRR

High Speed

9ꢀ

dB

freq = 60 Hz

16

6, 7

Package Characteristics

T = 2ꢀ°C unless otherwise speciﬁed.

A

Test

Conditions

Parameter

Symbol

Device

Min.

Typ.

10¹³

0.4

Max.

Units

Fig.

Note

Input-Output

Momentary-Withstand

Voltage*

V

ꢀ000

V rms

RH ≤ꢀ0%,

t = 1 min.

4, ꢀ

ISO

Resistance

(Input-Output)

R_I-O

10¹²

10¹¹

Ω

V_O= ꢀ00 VDC

T_A= 100°C,

4

V

_IO= ꢀ00 VDC

Capacitance

C_I-O

0.6

pF

f = 1 MHz

(Input-Output)

*The Input-Output Momentary Withstand Voltage is a dielectric voltage rating that should not be interpreted as an input-output continuous

voltage rating. For the continuous voltage rating refer to the VDE 0884 Insulation Characteristics Table (if applicable), your equipment level safety

speciﬁcation, or Application Note 1074, “Optocoupler Input-Output Endurance Voltage.”

Notes:

1. K₃is calculated from the slope of the best ﬁt line of I_PD2vs. I_PD1with eleven equally distributed data points from ꢀnA to ꢀ0 μA. This is approxi-

mately equal to I_PD2/I_PD1at I_F= 10 mA.

2. BEST FIT DC NONLINEARITY (NL_BF) is the maximum deviation expressed as a percentage of the full scale output of a “best ﬁt”straight line from

a graph of I_PD2vs. I_PD1with eleven equally distributed data points from ꢀ nA to ꢀ0μA. I_PD2error to best ﬁt line is the deviation below and above

the best ﬁt line, expressed as a percentage of the full scale output.

3. ENDS FIT DC NONLINEARITY (NL_EF) is the maximum deviation expressed as a percentage of full scale output of a straight line from the ꢀ nA to

the ꢀ0 μA data point on the graph of I_PD2vs. I_PD1

.

4. Device considered a two-terminal device: Pins 1, 2, 3, and 4 shorted together and pins ꢀ, 6, 7, and 8 shorted together.

ꢀ. In accordance with UL 1ꢀ77, each optocoupler is proof tested by applying an insulation test voltage of ≥6000 V rms for ≥1 second (leakage

detection current limit, I_I-Oof ꢀ μA max.). This test is performed before the 100% production test for partial discharge (method b) shown in the

IEC/EN/DIN EN 60747-ꢀ-2 Insulation Characteris-tics Table (for Option #0ꢀ0 only).

6. Speciﬁc performance will depend on circuit topology and components.

7. IMRR is deﬁned as the ratio of the signal gain (with signal applied to V_INof Figure 16) to the isolation mode gain (with V_INconnected to input

common and the signal applied between the input and output commons) at 60 Hz, expressed in dB.

9

0.03

0.02

0.01

0.00

-0.01

1.06

1.04

1.02

1.00

0.98

0.02

0.015

0.01

= ERROR MEAN

= ERROR MEAN 2 ꢀ STD DEV

= NORM K3 MEAN

= NORM K3 MEAN 2 ꢀ STD DEV

0 V < V

PD

< 15 V

0.005

0.0

-0.005

-0.01

-0.015

-0.02

-0.03

0.96

0.94

= DELTA K3 MEAN

= DELTA K3 MEAN 2 ꢀ STD DEV

NORMALIZED TO BEST-FIT K3 AT T = 25°C,

A

T

= 25 °C, 0 V < V

< 15 V

50.0 60.0

– INPUT PHOTODIODE CURRENT – µA

A

PD

0 V < V

< 15 V

40.0

– INPUT PHOTODIODE CURRENT – µA

PD

0.0

10.0

20.0

30.0

40.0

0.0

10.0

20.0

30.0

50.0 60.0

-55

-25

5

35

T – TEMPERATURE – °C

A

65

95

125

I

PD1

Figure 2. Normalized K3 vs. input I_PD

.

Figure 3. K3 drift vs. temperature.

Figure 4. I_PD2error vs. input I_PD(see note 4).

0.035

0.03

1.2

0.02

-55°C

= NL 50TH PERCENTILE

BF

0 V < V

5 nA < I

< 15 V

< 50 µA

= NL 90TH PERCENTILE

BF

PD

1.1

-40°C

0.015

0.01

25°C

1.0

0.025

0.02

0.9

0.8

0.7

0.6

85°C

100°C

0.005

0.0

0.015

0.01

-0.005

-0.01

-0.015

-0.02

0.5

0.4

0.3

0.2

NORMALIZED TO K1 CTR

AT I = 10 mA, T = 25°C

0 V < V

5 nA < I

< 15 V

< 50 µA

F

A

PD

0.005

0 V < V

< 15 V

PD1

= DELTA NL MEAN

BF

= DELTA NL MEAN 2 ꢀ STD DEV

BF

0.00

-55

0.0 2.0 4.0 6.0 8.0 10.0 12.0 14.0 16.0

-25

5

35

65

95

125

-55

-25

5

35

65

95

125

T

– TEMPERATURE – °C

T

– TEMPERATURE – °C

I

F

– LED INPUT CURRENT – mA

A

Figure 6. NL_BFdrift vs. temperature.

Figure 7. Input photodiode CTR vs. LED input

current.

Figure 5. NL_BFvs. temperature.

10.0

100

1.8

T

= 25°C

V

= 15 V

A

I = 10 mA

F

PD

1.7

1.6

1.5

1.4

1.3

1.2

10

1

8.0

6.0

4.0

0.1

0.01

2.0

0.0

0.001

0.0001

-55

-25

5

35

65

95

125

1.20

1.30

1.40

1.50

1.60

-55

-25

5

35

65

95

125

T

– TEMPERATURE – °C

T

– TEMPERATURE – °C

V

– FORWARD VOLTAGE – VOLTS

A

F

Figure 8. Typical photodiode leakage vs.

temperature.

Figure 10. LED forward voltage vs. temperature.

Figure 9. LED input current vs. forward voltage.

10

1000

900

800

700

600

500

400

300

P

I

OUTPUT POWER – mV

INPUT CURRENT – mA

S

200

100

0

25

T

50

75

100 125 150 175

– CASE TEMPERATURE – °C

S

Figure 11. Thermal derating curve dependence of safety limiting value

with case temperature per IEC/EN/DIN EN 60747-5-2.

R2

R1

V

IN

+

-

V

A1

A2

+

I

PD1

I

PD2

OUT

PD1

PD2

-

LED

I

F

A) BASIC TOPOLOGY

V

R2

CC

C2

C1

R1

LED

R3

V

IN

-

V

A1

A2

PD1

PD2

OUT

+

B) PRACTICAL CIRCUIT

Figure 12. Basic isolation ampliﬁer.

V

CC

V

IN

-

V

OUT

+

A) POSITIVE INPUT

B) POSITIVE OUTPUT

V

IN

-

V

OUT

+

C) NEGATIVE INPUT

D) NEGATIVE OUTPUT

Figure 13. Unipolar circuit topologies.

11

V

CC2

CC1

V

IOS1

CC1

IOS2

V

IN

-

V

OUT

+

A) SINGLE OPTOCOUPLER

V

CC

-

+

V

IN

-

V

OUT

+

-

+

B) DUAL OPTOCOUPLER

Figure 14. Bipolar circuit topologies.

R2

+I

IN

R1

D1

-

V

PD2

PD1

+

OUT

+

LED

R3

-I

IN

A) RECEIVER

V

CC

R1

LED

+I

OUT

V

IN

R2

-

PD1

+

-

D1

Q1

PD2

+

R3

-I

OUT

B) TRANSMITTER

Figure 15. Loop-powered 4-20 mA current loop circuits.

12

V

+5 V

CC2

V

+5 V

CC1

R5

10 K

R7

470

LED

R2

68 K

R3

10 K

V

OUT

Q2

Q4

R1

2N3904

68 K

Q1

2N3906

Q3

2N3906

V

IN

R4

10

R6

10

PD1

PD2

Figure 16. High-speed low-cost analog isolator.

V

+15 V

V

+15 V

CC1

CC2

C3

0.1µ

C5

0.1µ

R4

2.2 K

R5

270

Q1

2N3906

R6

6.8 K

C1

P

C2

33

R2

R1

200 K

47

174 K

50 K

P

INPUT

BNC

OUTPUT

BNC

1%

1 %

7

4

7

4

-

2

3

2

3

6

PD1

PD2

A1

A2

LT1097

+

C6

0.1µ

C4

0.1µ

R3

33 K

D1

1N4150

V

-15 V

LED

V

-15 V

EE2

EE1

Figure 17. Precision analog isolation ampliﬁer.

C3 10 pf

C1 10 pf

R6

180 K

R7

50 K

R2

180 K

D1

R4

680

-

GAIN

OC1

PD2

+

OC1

PD1

OC1

LED

-

V

MAG

R1

50 K

V

+

IN

BALANCE

OC2

LED

OC2

PD1

OC2

PD2

+

-

R5

680

R3

180 K

D2

C2 10 pf

V

= +15 V

= -15 V

CC1

EE1

Figure 18. Bipolar isolation ampliﬁer.

13

C3 10 pf

C1 10 pf

R5

180 K

R6

50 K

D1

D3

-

GAIN

+

OC1

PD2

-

R4

680

V

R1

220 K

MAG

+

V

OC1

PD1

IN

R2

10 K

R3

4.7 K

OC1

LED

+

D2

-

D4

-

V

+

CC

C2 10 pf

+

-

R7

6.8 K

R8

2.2 K

V

SIGN

OC2

6N139

V

= +15 V

= -15 V

CC1

EE1

Figure 19. Magnitude/sign isolation ampliﬁer.

Figure 20. SPICE model listing.

14

0.001 µF

+ILOOP

HCNR200

LED

R5

80 kΩ

R1

10 kΩ

Z1

5.1 V

R4

100 Ω

V

CC

5.5 V

0.1 µF

HCNR200

PD1

LM158

+

-

2N3906

V

OUT

+

R2

10 kΩ

LM158

HCNR200

PD2

0.001 µF

-ILOOP

R3

25 Ω

2

Design Equations:

VOUT / ILOOP = K3 (Rꢀ R3) / R1 + R3)

K3 = K2 / K1 = Constant = 1

Note:

The two OP-AMPS shown are two separate LM1ꢀ8, and not two channels in a single dual package,

otherwise the loop side and output side will not be properly isolated.

Figure 21. 4 to 20 mA HCNR200 receiver circuit.

+I

LOOP

R8

100kΩ

12V~40V

4 ~ 20mA

Q3

2N3904

4mA (Vin=0.8V)

20mA(Vin=4V)

Vcc

5.5V

R2

150 Ω

Q2

C1

1nF

IC3

2N3904

C3

5V1

+

Q4

-

LM158

R6

LED/IC1

HCNR200

R1

80k Ω

150 Ω

R7

3k2Ω

Vin

0.8V~4V

“0” @ 2200Hz

“1” @ 1200Hz

IC2

R4

1nF

-

Q1

2N3906

10k Ω C2

LM158

PD1/IC1

+

R5

25 Ω

PD2/IC1

R3

10k Ω

- I

LOOP

Design Equations:

(ILOOP/Vin)=K3(Rꢀ+R3)/(RꢀR1)

K3 = K2/K1 = Constant ≈ 1

Note:

The two OP-AMPS shown are two separate LM1ꢀ8 IC’s, and NOT dual channels in a

single package, otherwise, the LOOP side and input side will not be properly isolated;

The ꢀV1 Zener should be properly selected to ensure that it conducts at 187μA;

Figure 22. 4 to 20 mA HCNR200 transmitter circuit.

1ꢀ

Theory of Operation

Figure 1 illustrates how the HCNR200/201 high-linearity

optocoupler is conﬁgured. The basic optocoupler con-

sists of an LED and two photodiodes. The LED and one of

the photodiodes (PD1) is on the input leadframe and the

other photodiode (PD2) is on the output leadframe. The

package of the optocoupler is constructed so that each

photodiode receives approximately the same amount of

light from the LED.

Notice that I_PD1depends ONLY on the input voltage and

the value of R1 and is independent of the light output

characteristics of the LED. As the light output of the

LED changes with temperature, ampliﬁer A1 adjusts I_F

to compensate and maintain a constant current in PD1.

Also notice that I_PD1is exactly proportional to V , giving

IN

a very linear relationship between the input voltage and

the photodiode current.

An external feedback ampliﬁer can be used with PD1 to

monitor the light output of the LED and automatically

adjust the LED current to compensate for any non-linear-

ities or changes in light output of the LED. The feedback

ampliﬁer acts to stabilize and linearize the light output

of the LED. The output photodiode then converts the

stable, linear light output of the LED into a current, which

can then be converted back into a voltage by another

ampliﬁer.

The relationship between the input optical power and

the output current of a photodiode is very linear. There-

fore, by stabilizing and linearizing I_PD1, the light output of

the LED is also stabilized and linearized. And since light

from the LED falls on both of the photodiodes, I_PD2will be

stabilized as well.

The physical construction of the package determines the

relative amounts of light that fall on the two photodiodes

and, therefore, the ratio of the photodiode currents. This

results in very stable operation over time and tempera-

ture. The photodiode current ratio can be expressed as a

constant, K, where

Figure 12a illustrates the basic circuit topology for

implementing a simple isolation ampliﬁer using the

HCNR200/201 optocoupler. Besides the optocoupler,

two external op-amps and two resistors are required.

This simple circuit is actually a bit too simple to function

properly in an actual circuit, but it is quite useful for ex-

plaining how the basic isolation ampliﬁer circuit works (a

few more components and a circuit change are required

to make a practical circuit, like the one shown in Figure

12b).

K = I_PD2/I_PD1

.

Ampliﬁer A2 and resistor R2 form a trans-resistance am-

pliﬁer that converts I_PD2back into a voltage, V_OUT, where

V_OUT= I_PD2*R2.

Combining the above three equations yields an overall

expression relating the output voltage to the input volt-

age,

The operation of the basic circuit may not be immedi-

ately obvious just from inspecting Figure 12a, particu-

larly the input part of the circuit. Stated brieﬂy, ampliﬁer

A1 adjusts the LED current (I_F), and therefore the current

in PD1 (I_PD1), to maintain its “+” input terminal at 0 V. For

example, increasing the input voltage would tend to in-

crease the voltage of the “+” input terminal of A1 above

0 V. A1 ampliﬁes that increase, causing I_Fto increase, as

well as I_PD1. Because of the way that PD1 is connected,

I_PD1will pull the “+” terminal of the op-amp back toward

ground. A1 will continue to increase I_Funtil its “+” termi-

nal is back at 0 V. Assuming that A1 is a perfect op-amp,

no current ﬂows into the inputs of A1; therefore, all of the

current ﬂowing through R1 will ﬂow through PD1. Since

the “+” input of A1 is at 0 V, the current through R1, and

therefore I_PD1as well, is equal to V_IN/R1.

V_OUT/V = K*(R2/R1).

IN

Therefore the relationship between V and V_OUTis con-

IN

stant, linear, and independent of the light output

characteristics of the LED. The gain of the basic isolation

ampliﬁer circuit can be adjusted simply by adjusting the

ratio of R2 to R1. The parameter K (called K₃in the electri-

cal speciﬁcations) can be thought of as the gain of the

optocoupler and is speciﬁed in the data sheet.

Remember, the circuit in Figure12a is simpliﬁed in order

to explain the basic circuit operation. A practical circuit,

more like Figure 12b, will require a few additional compo-

nents to stabilize the input part of the circuit, to limit the

LED current, or to optimize circuit performance. Example

application circuits will be discussed later in the data

sheet.

Essentially, ampliﬁer A1 adjusts I_Fso that

I_PD1= V /R1.

IN

16

Circuit Design Flexibility

Circuit design with the HCNR200/201 is very ﬂexible

because the LED and both photodiodes are accessible

to the designer. This allows the designer to make perf-

ormance trade-oﬀs that would otherwise be diﬃcult to

make with commercially available isolation ampliﬁers

(e.g., bandwidth vs. accuracy vs. cost). Analog isolation

circuits can be designed for applications that have either

unipolar (e.g., 0-10 V) or bipolar (e.g., 10 V) signals, with

positive or negative input or output voltages. Several

simpliﬁed circuit topologies illustrating the design ﬂex-

ibility of the HCNR200/201 are discussed below.

to worry about. However, the second circuit requires two

optocouplers, separate gain adjustments for the posi-

tive and negative portions of the signal, and can exhibit

crossover distortion near zero volts. The correct circuit to

choose for an application would depend on the require-

ments of that particular application. As with the basic

isolation ampliﬁer circuit in Figure 12a, the circuits in Fig-

ure 14 are simpliﬁed and would require a few additional

components to function properly. Two example circuits

that operate with bipolar input signals are discussed in

the next section.

The circuit in Figure 12a is conﬁgured to be non-invert-

ing with positive input and output voltages. By simply

changing the polarity of one or both of the photodiodes,

the LED, or the op-amp inputs, it is possible to implement

other circuit conﬁgurations as well. Figure 13 illustrates

how to change the basic circuit to accommodate both

positive and negative input and output voltages. The in-

put and output circuits can be matched to achieve any

combination of positive and negative voltages, allowing

for both inverting and non-inverting circuits.

As a ﬁnal example of circuit design ﬂexibility, the simpli-

ﬁed schematics in Figure 1ꢀ illustrate how to implement

4-20 mA analog current-loop transmitter and receiver

circuits using the HCNR200/201 optocoupler. An impor-

tant feature of these circuits is that the loop side of the

circuit is powered entirely by the loop current, eliminat-

ing the need for an isolated power supply.

The input and output circuits in Figure 1ꢀa are the same

as the negative input and positive output circuits shown

in Figures 13c and 13b, except for the addition of R3 and

zener diode D1 on the input side of the circuit. D1 regu-

lates the supply voltage for the input ampliﬁer, while R3

forms a current divider with R1 to scale the loop current

down from 20 mA to an appropriate level for the input

circuit (<ꢀ0 μA).

All of the conﬁgurations described above are unipolar

(single polarity); the circuits cannot accommodate a sig-

nal that might swing both positive and negative. It is pos-

sible, however, to use the HCNR200/201 optocoupler to

implement a bipolar isolation ampliﬁer. Two topologies

that allow for bipolar operation are shown in Figure 14.

As in the simpler circuits, the input ampliﬁer adjusts the

LED current so that both of its input terminals are at the

same voltage. The loop current is then divided

The circuit in Figure14a uses two current sources to

oﬀset the signal so that it appears to be unipolar to the

optocoupler. Current source I_OS1provides enough oﬀset

to ensure that I_PD1is always positive. The second current

source, I_OS2, provides an oﬀset of opposite polarity to ob-

tain a net circuit oﬀset of zero. Current sources I_OS1and

I_OS2can be implemented simply as resistors connected to

suitable voltage sources.

between R1 and R3. I_PD1is equal to the current in R1 and

is given by the following equation:

I_PD1= I_LOOP*R3/(R1+R3).

Combining the above equation with the equations used

for Figure 12a yields an overall expression relating the

output voltage to the loop current,

The circuit in Figure14b uses two optocouplers to obtain

bipolar operation. The ﬁrst optocoupler handles the pos-

itive voltage excursions, while the second optocoupler

handles the negative ones. The output photodiodes are

connected in an antiparallel conﬁguration so that they

produce output signals of opposite polarity.

V_OUT/I_LOOP= K*(R2*R3)/(R1+R3).

Again, you can see that the relationship is constant, lin-

ear, and independent of the characteristics of the LED.

The 4-20 mA transmitter circuit in Figure 1ꢀb is a little dif-

ferent from the previous circuits, particularly the output

circuit. The output circuit does not directly generate an

output voltage which is sensed by R2, it instead uses Q1

to generate an output current which ﬂows through R3.

This output current generates a voltage across R3, which

is then sensed by R2. An analysis similar to the one above

yields the following expression relating output current

to input voltage:

The ﬁrst circuit has the obvious advantage of requiring

only one optocoupler; however, the oﬀset performance

of the circuit is dependent on the matching of I_OS1and

I_OS2and is also dependent on the gain of the optocoupler.

Changes in the gain of the optocoupler will directly af-

fect the oﬀset of the circuit.

The oﬀset performance of the second circuit, on the

other hand, is much more stable; it is independent of

optocoupler gain and has no matched current sources

I_LOOP/V = K*(R2+R3)/(R1*R3).

IN

17

The preceding circuits were presented to illustrate the

ﬂexibility in designing analog isolation circuits using the

HCNR200/201. The next section presents several com-

The circuit operates in the same way as the others. The

only major diﬀerences are the two compensation capaci-

tors and additional LED drive circuitry. In the high-speed

plete schematics to illustrate practical applications of the circuit discussed above, the input and output circuits are

HCNR200/201.

stabilized by reducing the local loop gains of the input

and output circuits. Because reducing the loop gains

would decrease the accuracy of the circuit, two compen-

sation capacitors, C1 and C2, are instead used to improve

circuit stability. These capacitors also limit the bandwidth

of the circuit to about 10 kHz and can be used to reduce

the output noise of the circuit by reducing its bandwidth

even further.

Example Application Circuits

The circuit shown in Figure 16 is a high-speed low-cost

circuit designed for use in the feedback path of switch-

mode power supplies. This application requires good

bandwidth, low cost and stable gain, but does not re-

quire very high accuracy. This circuit is a good example

of how a designer can trade oﬀ accuracy to achieve

improvements in bandwidth and cost. The circuit has a

bandwidth of about 1.ꢀ MHz with stable gain character-

istics and requires few external components.

The additional LED drive circuitry (Q1 and R3 through

R6) helps to maintain the accuracy and bandwidth of the

circuit over the entire range of input voltages. Without

these components, the transconductance of the LED

driver would decrease at low input voltages and LED

currents. This would reduce the loop gain of the input

circuit, reducing circuit accuracy and bandwidth. D1 pre-

vents excessive reverse voltage from being applied to

the LED when the LED turns oﬀ completely.

Although it may not appear so at ﬁrst glance, the circuit

in Figure 16 is essentially the same as the circuit in Fig-

ure 12a. Ampliﬁer A1 is comprised of Q1, Q2, R3 and R4,

while ampliﬁer A2 is comprised of Q3, Q4, Rꢀ, R6 and R7.

The circuit operates in the same manner as well; the only

diﬀerence is the performance of ampliﬁers A1 and A2.

The lower gains, higher input currents and higher oﬀset

voltages aﬀect the accuracy of the circuit, but not the

way it operates. Because the basic circuit operation has

not changed, the circuit still has good gain stability. The

use of discrete transistors instead of op-amps allowed

the design to trade oﬀ accuracy to achieve good band-

width and gain stability at low cost.

No oﬀset adjustment of the circuit is necessary; the gain

can be adjusted to unity by simply adjusting the ꢀ0 kohm

potentiometer that is part of R2. Any OP-97 type of op-

amp can be used in the circuit, such as the LT1097 from

Linear Technology or the AD70ꢀ from Analog Devices,

both of which oﬀer pA bias currents, μV oﬀset voltages

and are low cost. The input terminals of the op-amps and

the photodiodes are connected in the circuit using Kelvin

connections to help ensure the accuracy of the circuit.

To get into a little more detail about the circuit, R1 is se-

lected to achieve an LED current of about 7-10 mA at the

nominal input operating voltage according to the fol-

lowing equation:

The next two circuits illustrate how the HCNR200/201 can

be used with bipolar input signals. The isolation ampliﬁer

in Figure18 is a practical implementation of the circuit

shown in Figure 14b. It uses two optocouplers, OC1 and

OC2; OC1 handles the positive portions of the input sig-

nal and OC2 handles the negative portions.

I_F= (V /R1)/K1,

IN

where K₁(i.e., I_PD1/I_F) of the optocoupler is typically about

0.ꢀ%. R2 is then selected to achieve the desired output

voltage according to the equation,

Diodes D1 and D2 help reduce crossover distortion by

keeping both ampliﬁers active during both positive and

negative portions of the input signal. For example, when

the input signal positive, optocoupler OC1 is active while

OC2 is turned oﬀ. However, the ampliﬁer controlling OC2

is kept active by D2, allowing it to turn on OC2 more rap-

idly when the input signal goes negative, thereby reduc-

ing crossover distortion.

V_OUT/V = R2/R1.

IN

The purpose of R4 and R6 is to improve the dynamic re-

sponse (i.e., stability) of the input and output circuits by

lowering the local loop gains. R3 and Rꢀ are selected to

provide enough current to drive the bases of Q2 and Q4.

And R7 is selected so that Q4 operates at about the same

collector current as Q2.

Balance control R1 adjusts the relative gain for the posi-

tive and negative portions of the input signal, gain con-

trol R7 adjusts the overall gain of the isolation ampliﬁer,

and capacitors C1-C3 provide compensation to stabilize

the ampliﬁers.

The next circuit, shown in Figure17, is designed to achieve

the highest possible accuracy at a reasonable cost. The

high accuracy and wide dynamic range of the circuit is

achieved by using low-cost precision op-amps with very

low input bias currents and oﬀset voltages and is limited

by the performance of the optocoupler. The circuit is de-

signed to operate with input and output voltages from

1 mV to 10 V.

18

The ﬁnal circuit shown in Figure19 isolates a bipolar

analog signal using only one optocoupler and generates

two output signals: an analog signal proportional to the

magnitude of the input signal and a digital signal cor-

responding to the sign of the input signal. This circuit is

especially useful for applications where the output of

the circuit is going to be applied to an analog-to-digital

converter. The primary advantages of this circuit are very

good linearity and oﬀset, with only a single gain adjust-

ment and no oﬀset or balance adjustments.

HCNR200/201 SPICE Model

Figure 20 is the net list of a SPICE macro-model for the

HCNR200/201 high-linearity optocoupler. The macro-

model accurately reﬂects the primary characteristics of

the HCNR200/201 and should facilitate the design and

understanding of circuits using the HCNR200/201 opto-

coupler.

To achieve very high linearity for bipolar signals, the

gain should be exactly the same for both positive and

negative input polarities. This circuit achieves excellent

linearity by using a single optocoupler and a single input

resistor, which guarantees identical gain for both posi-

tive and negative polarities of the input signal. This pre-

cise matching of gain for both polarities is much more

diﬃcult to obtain when separate components are used

for the diﬀerent input polarities, such as is the previous

circuit.

The circuit in Figure19 is actually very similar to the pre-

vious circuit. As mentioned above, only one optocoupler

is used. Because a photodiode can conduct current in

only one direction, two diodes (D1 and D2) are used to

steer the input current to the appropriate terminal of

input photodiode PD1 to allow bipolar input currents.

Normally the forward voltage drops of the diodes would

cause a serious linearity or accuracy problem. However,

an additional ampliﬁer is used to provide an appropriate

oﬀset voltage to the other ampliﬁers that exactly cancels

the diode voltage drops to maintain circuit accuracy.

Diodes D3 and D4 perform two diﬀerent functions; the

diodes keep their respective ampliﬁers active indepen-

dent of the input signal polarity (as in the previous cir-

cuit), and they also provide the feedback signal to PD1

that cancels the voltage drops of diodes D1 and D2.

Either a comparator or an extra op-amp can be used to

sense the polarity of the input signal and drive an inex-

pensive digital optocoupler, like a 6N139.

It is also possible to convert this circuit into a fully bipolar

circuit (with a bipolar output signal) by using the output

of the 6N139 to drive some CMOS switches to switch the

polarity of PD2 depending on the polarity of the input

signal, obtaining a bipolar output voltage swing.

For product information and a complete list of distributors, please go to our website: www.avagotech.com

Avago, Avago Technologies, and the A logo are trademarks of Avago Technologies in the United States and other countries.

AV02-0886EN - December 10, 2011

型号:	HCNR201-300E
是否无铅：	不含铅
是否Rohs认证：	符合
生命周期：	Active
包装说明：	0.4 INCH, ROHS COMPLIANT, SURFACE MOUNT, DIP-8
Reach Compliance Code：	compliant
ECCN代码：	EAR99
HTS代码：	8541.40.80.00
风险等级：	0.49
配置：	DUAL, SIMULTANEOUS OPERATION
最大正向电流：	0.025 A
最大正向电压：	1.85 V
最大绝缘电压：	5000 V
JESD-609代码：	e3
安装特点：	THROUGH HOLE MOUNT
元件数量：	1
功能数量：	1
最高工作温度：	85 °C
最低工作温度：	-40 °C
光电设备类型：	OPTOELECTRONIC DEVICE
子类别：	Optocoupler - Transistor Outputs
表面贴装：	NO
端子面层：	Matte Tin (Sn)
Base Number Matches：	1

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