OP37EZ芯片引脚定义引脚图及功能IC贸易商引脚图技术参数-中国IC网-芯三七

Low Noise, Precision, High Speed

a

>

Operational Amplifier (A _VCL5)

OP37

FEATURES

The output stage has good load driving capability. A guaranteed

swing of 10 V into 600 Ω and low output distortion make the

OP37 an excellent choice for professional audio applications.

Low Noise, 80 nV p-p (0.1 Hz to 10 Hz)

3 nV/√Hz @ 1 kHz

Low Drift, 0.2 ␮V/؇C

High Speed, 17 V/␮s Slew Rate

63 MHz Gain Bandwidth

Low Input Offset Voltage, 10 ␮V

Excellent CMRR, 126 dB (Common-Voltage @ 11 V)

High Open-Loop Gain, 1.8 Million

Replaces 725, OP-07, SE5534 In Gains > 5

Available in Die Form

PSRR and CMRR exceed 120 dB. These characteristics, coupled

with long-term drift of 0.2 µV/month, allow the circuit designer

to achieve performance levels previously attained only by

discrete designs.

Low-cost, high-volume production of the OP37 is achieved by

using on-chip zener-zap trimming. This reliable and stable offset

trimming scheme has proved its effectiveness over many years of

production history.

GENERAL DESCRIPTION

The OP37 brings low-noise instrumentation-type performance to

such diverse applications as microphone, tapehead, and RIAA

phono preamplifiers, high-speed signal conditioning for data

acquisition systems, and wide-bandwidth instrumentation.

The OP37 provides the same high performance as the OP27,

but the design is optimized for circuits with gains greater than

five. This design change increases slew rate to 17 V/µs and

gain-bandwidth product to 63 MHz.

PIN CONNECTIONS

The OP37 provides the low offset and drift of the OP07

plus higher speed and lower noise. Offsets down to 25 µV and

drift of 0.6 µV/°C maximum make the OP37 ideal for preci-

sion instrumentation applications. Exceptionally low noise

(e_n= 3.5 nV/ @ 10 Hz), a low 1/f noise corner frequency of

2.7 Hz, and the high gain of 1.8 million, allow accurate

high-gain amplification of low-level signals.

8-Lead Hermetic DIP

(Z Suffix)

Epoxy Mini-DIP

(P Suffix)

8-Lead SO

(S Suffix)

The low input bias current of 10 nA and offset current of 7 nA

are achieved by using a bias-current cancellation circuit. Over

the military temperature range this typically holds I_Band I_OS

to 20 nA and 15 nA respectively.

1

2

3

4

8

7

6

5

V

TRIM

V

TRIM

–IN

+IN

V–

OS

OP37

V+

OUT

NC

NC = NO CONNECT

SIMPLIFIED SCHEMATIC

V+

C2

R3

R4

1

8

Q6

Q22

Q46

C1

V

ADJ.

OS

R23 R24

Q24

R1*

R2*

Q21

Q23

R9

R12

Q20 Q19

OUTPUT

Q1A Q1B

Q2B Q2A

NON-INVERTING

INPUT (+)

C3

C4

R5

Q3

Q26

INVERTING

INPUT (–)

Q45

Q11 Q12

Q27

Q28

*R1 AND R2 ARE PERMANENTLY

ADJUSTED ATWAFERTEST FOR

MINIMUM OFFSETVOLTAGE.

V–

REV. A

Information furnished by Analog Devices is believed to be accurate and

reliable. However, no responsibility is assumed by Analog Devices for its

use, norforanyinfringementsofpatentsorotherrightsofthirdpartiesthat

may result from its use. No license is granted by implication or otherwise

under any patent or patent rights of Analog Devices.

One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.

Tel: 781/329-4700

Fax: 781/326-8703

www.analog.com

OP37

ABSOLUTE MAXIMUM RATINGS⁴

ORDERING GUIDE

Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22 V

Internal Voltage (Note 1 ) . . . . . . . . . . . . . . . . . . . . . . . . . 22 V

Output Short-Circuit Duration . . . . . . . . . . . . . . . . . Indefinite

Differential Input Voltage (Note2) . . . . . . . . . . . . . . . . . 0.7 V

Differential Input Current (Note 2) . . . . . . . . . . . . . . . . 25 mA

Storage Temperature Range . . . . . . . . . . . . . –65°C to +150°C

Operating Temperature Range

T_A= 25°C

V_OSMAX

(µV)

Operating

Temperature

Range

CerDIP

8-Lead

Plastic

8-Lead

25

60

100

OP37AZ*

OP37EZ

MIL

OP37EP

OP37FP*

OP37GP

OP37GS

IND/COM

XIND

OP37A . . . . . . . . . . . . . . . . . . . . . . . . . . . –55°C to +1 25°C

OP37E (Z) . . . . . . . . . . . . . . . . . . . . . . . . . . –25°C to +85°C

OP37E, OP-37F (P) . . . . . . . . . . . . . . . . . . . . . 0°C to 70°C

OP37G (P, S, Z) . . . . . . . . . . . . . . . . . . . . . –40°C to +85°C

Lead Temperature Range (Soldering, 60 sec) . . . . . . . . 300°C

Junction Temperature . . . . . . . . . . . . . . . . . . –45°C to +150°C

3

OP37GZ

XIND

*Not for new design, obsolete, April 2002.

Package Type

␪

Unit

JA

JC

8-Lead Hermetic DIP (Z) 148

16

43

°C/W

8-Lead Plastic DIP (P)

8-Lead SO (S)

103

158

NOTES

¹For supply voltages less than 22 V, the absolute maximum input voltage is equal

to the supply voltage.

²The OP37’s inputs are protected by back-to-back diodes. Current limiting resistors

are not used in order to achieve low noise. If differential input voltage exceeds 0.7 V,

the input Current should be limited to 25 mA.

3

␪

_JAis specified for worst case mounting conditions, i.e., ␪_JAis specified for device

in socket for TO, CerDIP, P-DIP, and LCC packages; ␪_JAis specified for device

soldered to printed circuit board for SO package.

⁴Absolute maximum ratings apply to both DICE and packaged parts, unless

otherwise noted.

CAUTION

ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily

accumulate on the human body and test equipment and can discharge without detection. Although

the OP37 features proprietary ESD protection circuitry, permanent damage may occur on

devices subjected to high-energy electrostatic discharges. Therefore, proper ESD precautions

are recommended to avoid performance degradation or loss of functionality.

WARNING!

ESD SENSITIVE DEVICE

–2–

REV. A

OP37

SPECIFICATIONS ( V_S= ꢀ15 V, T_A= 25ꢁC, unless otherwise noted.)

OP37A/E

OP37F

Min Typ Max

OP37G

Min Typ Max

Parameter

Symbol

Conditions

Min Typ Max

Unit

Input Offset

Voltage

Long-Term

Stability

Input Offset

Current

Input Bias

Current

V_OS

Note 1

10

0.2

7

25

1.0

35

20

0.3

9

60

1.5

50

30

0.4

12

100

2.0

75

µV

V_OS/Time Notes 2, 3

µV/Mo

nA

I_OS

I_B

e_np-p

10

40

12

55

15

80

nA

Input Noise

Voltage

Input Noise

1 Hz to 10 Hz^{3, 5}

0.08 0.18

0.09 0.25

µV p-p

Voltage Density e_n

f_O= 10 Hz³

f_O= 30 Hz³

f_O= 1000 Hz³

3.5

3.1

3.0

5.5

4.5

3.8

3.5

3.1

3.0

5.5

4.5

3.8

3.3

3.2

8.0

5.6

4.5

nV/√ Hz

pA/√ Hz

Input Noise

CurrentDensity i_N

f_O= 10 Hz^{3, 6}

1.7

1.0

0.4

4.0

2.3

0.6

1.7

1.0

0.4

4.0

2.3

0.6

1.7

1.0

0.4

f

_O= 30 Hz^{3, 6}

f_O= 1000 Hz^{3, 6}

0.6

Input Resistance

Differential

Mode

R_IN

Note 7

1.3

6

3

0.9

4 5

2.5

0.7

4

2

MΩ

GΩ

V

Input Resistance

Common Mode

Input Voltage

Range

Common Mode

Rejection Ratio

Power Supply

Rejection Ratio

R_INCM

IVR

11

114

12.3

11

106

12.3

11

12.3

CMRR

PSSR

V_CM

=

11 V

126

1

123

1

100

120

2

dB

V_S= 4 V

to 18 V

10

20

µV/ V

Large Signal

Voltage Gain

A_VO

R_L≥ 2 kΩ,

V_O= 10 V

R_L≥ 1 kΩ,

Vo = 10 V

R_L≥ 600 Ω,

1000 1800

700

400

1500

V/m V

800

1500

800

1500

V_O

= 1 V,

V_S4⁴

250

700

250

700

200

500

V/m V

Output Voltage

Swing

V_O

R_L≥ 2 kΩ

R_L≥ 600 Ω

R_L≥ 2k Ω⁴

12.0 13.8

10 11.5

11 17

12.0 13.8

10 11.5

11 17

11.5 13.5

10 11.5

11 17

V

V/µs

Slew Rate

Gain Bandwidth

Product

SR

GBW

f

_O= 10 kHz⁴

45

63

40

45

63

40

45

63

40

MHz

f_O= 1 MHz

V_O= 0, I_O= 0

V_O= 0

Open-Loop

Output Resistance R_O

Power

Consumption

Offset Adjustment

Range

70

90

4

70

90

4

70

100

4

Ω

P_d

140

170

mW

mV

R_P= 10 kΩ

NOTES

¹Input offset voltage measurements are performed by automated test equipment approximately 0.5 seconds after application of power. A/E grades guaranteed fully

warmed up.

²Long term input offset voltage stability refers to the average trend line of V_OSvs. Time over extended periods after the first 30 days of operation. Excluding the initial

hour of operation, changes in V_OSduring the first 30 days are typically 2.5 µV—refer to typical performance curve.

³Sample tested.

⁴Guaranteed by design.

⁵See test circuit and frequency response curve for 0.1 Hz to 10 Hz tester.

⁶See test circuit for current noise measurement.

⁷Guaranteed by input bias current.

–3–

REV. A

OP37–SPECIFICATIONS

Electrical Characteristics ( V_S= ꢀ15 V, –55ꢁC < T_A< +125ꢁC, unless otherwise noted.)

OP37A

Typ

OP37C

Parameter

Symbol

Conditions

Min

Max

Min

Typ

Max

Unit

Input Offset

Voltage

Average Input

Offset Drift

V_OS

Note 1

1025

30

100

µV

TCV_OS

TCV_OSN

Note 2

Note 3

0.2

0.6

60

0.4

135

35

1.8

nA

µV/°C

Input Offset

Current

Input Bias

I_OS

1550

20

30

Current

I_B

150

nA

V

Input Voltage

Range

Common Mode

Rejection Ratio

Power Supply

Rejection Ratio

IVR

CMRR

PSRR

10.3

11.5

122

10.2 11.5

116

V_CM

=

10 V

108

94

4

dB

V_S= 4.5 V to

18 V

2 16

51

µV/ V

Large-Signal

Voltage Gain

A_VO

V_O

R_L≥ 2 kΩ,

V_O

=

10 V

600

1200

13.5

300

10.5

800

13.0

V/m V

V

Output Voltage

Swing

R_L≥ 2 kΩ

11.5

Electrical Characteristics ^{(V = ꢀ15 V, –25ꢁC < T < +85ꢁC for OP37EZ/FZ, 0ꢁC < T < 70ꢁC for OP37EP/FP, and –40ꢁC < T}

< +85ꢁC for OP37GP/GS/GZ, unless otherwise noted.)

S

A

OP37E

Min Typ Max

OP37F

Min Typ Max

OP37C

Parameter

Symbol

Conditions

Min Typ Max

Unit

Input Offset

Voltage

Average Input

Offset Drift

V_OS

20

50

40

140

55

220

µV

TCV_OS

TCV_OSN

Note 2

Note 3

0.2

10

0.6

50

0.3

14

1.3

85

95

0.4

20

1.8

µV/°C

nA

Input Offset

Current

Input Bias

Current

Input Voltage

Range

I_OS

I_B

135

14

10.5 11.8

60

18

10.5 11.8

25

10.5 11.8

150

nA

IVR

V

Common Mode

Rejection Ratio CMRR

Power Supply

Rejection Ratio PSRR

V_CM

=

10 V

108

122

2

100

119

2

94

116

4

dB

V_S= 4.5 V to

18 V

15

16

32

µV/ V

Large-Signal

Voltage Gain

A_VO

V_O

R_L≥ 2 kΩ,

VO

=

10 V

750

1500

700

1300

450

11

1000

13.3

V/mV

V

Output Voltage

Swing

R_L≥ 2 kΩ

11.7 13.6

11.4 13.5

NOTES

¹Input offset voltage measurements are performed by automated test equipment approximately 0.5 seconds after application of power. A/E grades guaranteed fully

warmed up.

²The TC _VOSperformance is within the specifications unnulled or when nulled withR_P= 8 kΩ to 20 kΩ. TC _VOSis 100% tested for A/E grades, sample tested for F/G grades.

³Guaranteed by design.

–4–

REV. A

OP37

1. NULL

2. (–) INPUT

3. (+) INPUT

4. V–

6. OUTPUT

7. V+

8. NULL

(V_S= ꢀ15 V, T_A= 25ꢁC for OP37N, OP37G, and OP37GR devices; T_A= 125ꢁC for OP37NT and OP37GT devices,

unless otherwise noted.)

Wafer Test Limits

OP37NT

Limit

OP37N

Limit

OP37GT

Limit

OP37G

Limit

OP37GR

Limit

Parameter

Symbol

Conditions

Unit

Input Offset

Voltage

Input Offset

Current

Input Bias

Current

Input Voltage

Range

Common Mode

Rejection Ratio CMRR

V_OS

I_OS

I_B

Note 1

60

35

200

85

60

100

75

µV MAX

nA MAX

V MIN

50

60

40

11

114

95

55

11

106

80

IVR

10.3

100

11

V_CM

=

11 V 108

100

dB MIN

Power Supply

Rejection Ratio PSRR

T_A= 25°C,

V_S= 4 V to

18 V

10

20

µV/V MAX

T_A= 125°C,

V_S= 4.5 V to

18 V

16

20

Large-Signal

Voltage Gain

A_VO

R_L≥ 2 kΩ,

V_O

=

10 V

600

1000

800

500

1000

800

700

V/mV MIN

R_L≥ 1 kΩ,

V_O10 V

=

Output Voltage

Swing

V_O

P_d

R_L≥ 2 kΩ

11.5

12

10

11

12

10

11.5

10

V MIN

R_L≥ 600 kΩ

Power

Consumption

V_O= 0

140

170

mW MAX

NOTES

For 25°C characterlstics of OP37NT and OP37GT devices, see OP37N and OP37G characteristics, respectively.

Electrical tests are performed at wafer probe to the limits shown. Due to variations in assembly methods and normal yield loss, yield after packaging is not guaranteed

for standard product dice. Consult factory to negotiate specifications based on dice lot qualification through sample lot assembly and testing.

REV. A

–5–

OP37

(V = ꢀ15 V, T = 25ꢁC, unless otherwise noted.)

Typical Electrical Characteristics

S

A

OP37NT

Typical

OP37N

Typical

OP37GT

Typical

OP37G

Typical

OP37GR

Typical

Parameter

Symbol

Conditions

Unit

Average Input

Offset Voltage

Drift

TCV_OSor Nulled or

TCV_OSN

Unnulled

R_P= 8 kΩ

to 20 kΩ

0.2

80

0.2

80

0.3

0.4

µV/°C

pA/°C

Average Input

Offset Current

Drift

Average Input

Bias Current

Drift

TCI_OS

TCI_B

130

160

130

160

180

200

100

Input Noise

Voltage Density e_n

f_O= 10 Hz

f_O= 30 Hz

3.5

3.1

3.0

3.5

3.1

3.0

3.5

3.1

3.0

3.5

3.1

3.0

3.8

3.3

3.2

nV/√Hz

f

_O= 1000 Hz

Input Noise

Current Density i_n

f_O= 10 Hz

f_O= 30 Hz

1.7

1.0

0.4

1.7

1.0

0.4

1.7

1.0

0.4

1.7

1.0

0.4

1.7

1.0

0.4

pA/√ Hz

f

_O= 1000 Hz

Input Noise

Voltage

e_{n p-p}

0.1 Hz to

10 Hz

R_L≥ 2k Ω

0.08

17

0.08

17

0.08

17

0.08

17

0.09

17

µV p-p

V/µs

Slew Rate

Gain Bandwidth

Product

SR

GBW

f_O= 10 kHz

63

MHz

–6–

REV. A

Typical Performance Characteristics–OP37

10

9

100

90

80

70

60

50

40

30

T

V

= 25ꢁC

= ꢀ15V

A

8

741

S

7

6

5

4

I/F CORNER

LOW NOISE

10

I/F CORNER =

2.7Hz

3

2

AUDIO OP AMP

OP37

I/F CORNER

I/F CORNER = 2.7Hz

TEST TIME OF 10sec MUST BE USED

TO LIMIT LOW FREQUENCY

(<0.1Hz) GAIN.

INSTRUMENTATION AUDIO RANGE

RANGETO DC

TO 20kHz

1

10

100

1k

1

10

100

1k

0.01

0.1

1

10

100

FREQUENCY – Hz

TPC 1. Noise-Tester Frequency

Response (0.1 Hz to 10 Hz)

TPC 2. Voltage Noise Density vs.

Frequency

TPC 3. A Comparison of Op Amp

Voltage Noise Spectra

100

10

5

R1

R2

T

V

= 25ꢁC

= ꢀ15V

A

T

V

= 25ꢁC

= ꢀ15V

V

= ꢀ15V

A

S

4

3

2

1

R

– 2R1

S

AT 10Hz

AT 1kHz

1

10

0.1

AT 10Hz

AT 1kHz

RESISTOR NOISE ONLY

1

100

0.01

100

–50 –25

0

25

50

75

100 125

1k

10k

1k

10k

100k

TEMPERATURE – ꢁC

SOURCE RESISTANCE – ꢃ

BANDWIDTH – Hz

TPC 4. Input Wideband Voltage Noise

vs. Bandwidth (0.1 Hz to Frequency

Indicated)

TPC 5. Total Noise vs. Source Resistance

TPC 6. Voltage Noise Density vs.

Temperature

5

10.0

5.0

4.0

T

= 25ꢁC

A

4

3

2

1

AT 10Hz

AT 1kHz

T

= +125ꢁC

A

3.0

2.0

1.0

T

= –55ꢁC

A

T

= +25ꢁC

A

I/F CORNER = 140Hz

0.1

10

0

10

20

30

40

5

15

25

35

45

100

1k

10k

TOTAL SUPPLYVOLTAGE (V+ – V–) – Volts

TOTAL SUPPLYVOLTAGE – Volts

FREQUENCY – Hz

TPC 7. Voltage Noise Density vs.

Supply Voltage

TPC 8. Current Noise Density vs.

Frequency

TPC 9. Supply Current vs. Supply

Voltage

–7–

REV. A

OP37

6

4

60

50

40

OP37C

OP37B

T

= 25ꢁC

A

V

= ꢀ15V

S

2

10

30

20

0

OP37A

–2

–4

OP37C/G

OP37F

10

0

OP37B

OP37A

–6

6

–10

–20

–30

OP37A

OP37B

5

4

OP37A/E

2

–40

0

TRIMMINGWITH

10kꢃ POT DOES

–2

–50

–60

–70

NOT CHANGE

–4

–6

TCV

OS

OP37C

1

–75 –50 –25

0

25 50 75 100 125 150 175

0

1

2

3

4

5

0

1

2

3

4

5

6

7

TEMPERATURE – ꢁC

TIME AFTER POWER ON – MINUTES

TIME – MONTHS

TPC 10. Offset Voltage Drift of Eight

Representative Units vs. Temperature

TPC 12. Warm Up Offset Voltage Drift

TPC 11. Long-Term Offset Voltage

Drift of Six Representative Units

30

50

V

= +15V

S

V

= +15V

V = ꢀ15V

S

25

20

40

30

20

10

40

30

20

T

25ꢁC

=

T = 70ꢁC

A

THERMAL SHOCK

RESPONSE BAND

15

10

5

OP37C

OP37B

10

0

DEVICE IMMERSED

IN 70ꢁC OIL BATH

OP37B

OP37A

25

0

–20

0

20

40

100

60

80

–75 –50 –25

0

50 75 100 125

–50 –25

0

25 50 75 100 125 150

TEMPERATURE – ꢁC

TIME – Seconds

TEMPERATURE – ꢁC

TPC 13. Offset Voltage Change Due

to Thermal Shock

TPC 14. Input Bias Current vs. Temperature

TPC 15. Input Offset Current vs.

Temperature

80

75

70

65

60

55

30

25

90

60

50

40

30

20

10

0

–80

140

T

V

= 25ꢁC

= ꢀ15V

A

V

= ꢀ15V

T

V

R

= 25ꢁC

= ꢀ15V

2kꢃ

S

A

85

80

75

70

65

S

ꢄM

–100

–120

–140

–160

–180

–200

–220

120

100

80

60

40

20

0

S

L

PHASE

MARGIN

= 71ꢁ

GBW

60

55

A

= 5

V

50

45

40

20

15

10

SLEW

–10

100k

2

3

4

5

6

7

8

1

10

–50 –25

0

25

50

75

100 125

10

10 10

10

10 10 10

1M

10M

100M

FREQUENCY – Hz

TEMPERATURE – ꢁC

TPC 16. Open-Loop Gain vs. Frequency

TPC 17. Slew Rate, Gain Bandwidth

Product, Phase Margin vs. Temperature

TPC 18. Gain, Phase Shift vs. Frequency

–8–

REV. A

OP37

2.5

2.0

1.5

1.0

0.5

0

28

24

20

16

12

8

18

16

T

V

= 25ꢁC

= ꢀ15V

T

= 25ꢁC

A

S

POSITIVE

SWING

14

12

10

8

R

= 2kꢃ

L

NEGATIVE

SWING

R

= 1kꢃ

L

6

4

2

T

= 25ꢁC

4

A

0

V

= ꢀ15V

S

–2

100

0

10

0

10

20

30

40

50

4

5

6

7

10

1k

10k

10

TOTAL SUPPLYVOLTAGE – Volts

LOAD RESISTANCE – ꢃ

FREQUENCY – Hz

TPC 19. Open-Loop Voltage Gain vs.

Supply Voltage

TPC 20. Maximum Output Swing vs.

Frequency

TPC 21. Maximum Output Voltage

vs. Load Resistance

80

60

40

1µs

5V

200ns

20mV

+50mV

0V

+10V

0V

T

V

A

= 25ꢁC

= ꢀ15V

= +5

A

T

V

A

= 25ꢁC

= ꢀ15V

= +5 (1kꢃ, 250ꢃ)

A

–10V

S

V

A

= ꢀ15V

= 20mV

= +5 (1kꢃ, 250ꢃ)

20

0

S

–50mV

V

IN

V

(1kꢃ, 250ꢃ)

V

0

500

1000

1500

2000

CAPACITIVE LOAD – pF

TPC 22. Small-Signal Overshoot vs.

Capacitive Load

TPC 23. Large-Signal Transient

Response

TPC 24. Small-Signal Transient

Response

60

140

16

V

T

= ꢀ15V

= 25ꢁC

= ꢀ10V

T

V

= 25ꢁC

= ꢀ15V

S

A

T = –55ꢁC

A

12

8

A

S

V

T

= +25ꢁC

120

100

80

CM

A

50

40

30

20

10

T

= +125ꢁC

A

4

I

(+)

SC

0

T

= –55ꢁC

A

–4

–8

–12

–16

I

(–)

SC

T

= +25ꢁC

A

60

T

= +125ꢁC

ꢀ10

A

40

1k

0

1

2

3

4

5

0

ꢀ5

ꢀ15

ꢀ20

10k

100k

FREQUENCY – Hz

1M

10M

TIME FROM OUTPUT SHORTEDTO

SUPPLYVOLTAGE – Volts

GROUND – MINUTES

TPC 25. Short-Circuit Current vs. Time

TPC 26. CMRR vs. Frequency

TPC 27. Common-Mode Input Range

vs. Supply Voltage

–9–

REV. A

OP37

2.4

2.2

2.0

1.8

1.6

1.4

1.2

1.0

0.8

0.1ꢂF

T

V

= 25ꢁC

= ꢀ15V

A

1 SEC/DIV

S

100kꢃ

OP37

10ꢃ

D.U.T.

2kꢃ

VOLTAGE

GAIN

= 50,000

22ꢂF

4.3kꢃ

2.2ꢂF

OP12

100kꢃ

SCOPE ꢅ 1

= 1Mꢃ

4.7ꢂF

R

IN

110kꢃ

0.6

0.4

0.1ꢂF

24.3kꢃ

100

1k

10k

100k

LOAD RESISTANCE – ꢃ

TPC 28. Noise Test Circuit (0.1 Hz to

10 Hz)

TPC 29. Low-Frequency Noise

TPC 30. Open-Loop Voltage Gain vs.

Load Resistance

160

19

18

17

20

T

= 25ꢁC

A

T

V

A

V

= 25ꢁC

= ꢀ15V

= 5

T = 25ꢁC

A

140

RISE

FALL

A

= 5

S

VCL

V

120

100

80

60

40

20

0

15

10

5

= 20V p-p

O

NEGATIVE

SWING

POSITIVE

SWING

16

15

0

ꢀ3

1

10 100 1k 10k 100k 1M 10M 100M

100

1k

10k

100k

ꢀ6

ꢀ9

ꢀ12

ꢀ15

ꢀ18

ꢀ21

FREQUENCY – Hz

LOAD RESISTANCE – ꢃ

SUPPLYVOLTAGE – Volts

TPC 31. PSRP vs. Frequency

TPC 32. Slew Rate vs. Load

TPC 33. Slew Rate vs. Supply Voltage

–10–

REV. A

OP37

APPLICATIONS INFORMATION

Noise Measurements

OP37 Series units may be inserted directly into 725 and OP07

sockets with or without removal of external compensation or

nulling components. Additionally, the OP37 may be fitted to

unnulled 741type sockets; however, if conventional 741 nulling

circuitry is in use, it should be modified or removed to ensure

correct OP37 operation. OP37 offset voltage may be nulled to

zero (or other desired setting) using a potentiometer (see offset

nulling circuit).

To measure the 80 nV peak-to-peak noise specification of the

OP37 in the 0.1 Hz to 10 Hz range, the following precautions

must be observed:

• The device has to be warmed-up forat least five minutes. As

shown in the warm-up drift curve, the offset voltage typically

changes 4 µV due to increasing chip temperature after power up.

In the ten second measurement interval, these temperature-

induced effects can exceed tens of nanovolts.

The OP37 provides stable operation with load capacitances of

up to 1000 pF and 10 V swings; larger capacitances should be

decoupled with a 50 Ω resistor inside the feedback loop. Closed

loop gain must be at least five. For closed loop gain between five

to ten, the designer should consider both the OP27 and the OP37.

For gains above ten, the OP37 has a clear advantage over the

unity stable OP27.

• For similar reasons, the device has to be well-shielded from

air currents. Shielding minimizes thermocouple effects.

• Sudden motion in the vicinity of the device can also

“feedthrough” to increase the observed noise.

• The test time to measure 0.1 Hz to l0 Hz noise should not

exceed 10 seconds. As shown in the noise-tester frequency

response curve, the 0.1 Hz corner is defined by only one zero.

The test time of ten seconds acts as an additional zero to eliminate

noise contributions from the frequency band below 0.1 Hz.

Thermoelectric voltages generated by dissimilar metals at the input

terminal contacts can degrade the drift performance. Best

operation will be obtained when both input contacts are main-

tained at the same temperature.

• A noise-voltage-density test is recommended when measuring

noise on a large number of units. A 10 Hz noise-voltage-density

measurement will correlate well with a 0.1 Hz-to-10 Hz peak-to-peak

noise reading, since both results are determined by the white

noise and the location of the 1/f corner frequency.

10kꢃ R

P

V+

–

OP37

OUTPUT

Optimizing Linearity

+

Best linearity will be obtained by designing for the minimum

output current required for the application. High gain and

excellent linearity can be achieved by operating the op amp with

a peak output current of less than 10 mA.

V–

Figure 1. Offset Nulling Circuit

Offset Voltage Adjustment

Instrumentation Amplifier

A three-op-amp instrumentation amplifier provides high gain and

wide bandwidth. The input noise of the circuit below is 4.9 nV/√Hz.

The gain of the input stage is set at 25 and the gain of the second

stage is 40; overall gain is 1000. The amplifier bandwidth of

800 kHz is extraordinarily good for a precision instrumentation

amplifier. Set to a gain of 1000, this yields a gain bandwidth

product of 800 MHz. The full-power bandwidth for a 20 V p-p

output is 250 kHz. Potentiometer R7 provides quadrature

trimming to optimize the instrumentation amplifier’s ac common-

mode rejection.

The input offset voltage of the OP37 is trimmed at wafer level.

However, if further adjustment of V_OSis necessary, a 10 kΩ trim

potentiometer may be used. TCV_OSis not degraded (see offset

nulling circuit). Other potentiometer values from 1 kΩ to 1 MΩ

can be used with a slight degradation (0.1 µV/°C to 0.2 µV/°C) of

TCV_OS. Trimming to a value other than zero creates a drift of

approximately (V_OS/300) µV/°C. For example, the change in TCV_OS

will be 0.33 µV/°C if V_OSis adjusted to 100 µV. The offset voltage

adjustment range with a 10 kΩ potentiometer is 4 mV. If smaller

adjustment range is required, the nulling sensitivity can be reduced

by using a smaller pot in conjunction with fixed resistors. For

example, the network below will have a 280 µV adjustment range.

R5

500ꢃ

0.1%

R8

20kꢃ

0.1%

+

INPUT (–)

OP37

–

R1

4.7kꢃ

1kꢃ POT

4.7kꢃ

8

1

5kꢃ

0.1%

R3

V+

–

390ꢃ

R7

V

OUT

R4

5kꢃ

0.1%

100kꢃ OP37

C1

100pF

R2

100ꢃ

Figure 2. TBD

+

+18V

R6

R9

19.8kꢃ

500ꢃ

0.1%

–

OP37

R10

500ꢃ

INPUT (+)

+

NOTES:

TRIM R2 FOR A

OP37

= 1000

VCL

TRIM R10 FOR dc CMRR

TRIM R7 FOR MINIMUMV

AT V

= 20V p-p, 10kHz

CM

OUT

Figure 4a. TBD

–18V

Figure 3. Burn-In Circuit

REV. A

–11–

OP37

140

1k

T

= 25ꢁC

A

OP08/108

5534

V

= ꢀ15V

= 20V p-p

S

R

= 0

S

500

V

CM

120

100

80

ACTRIM @ 10kHz

= 0

R

S

OP07

1

R

= 1kꢃ

S

BALANCED

2

100

50

OP27/37

R

= 100ꢃ,

1kꢃ UNBALANCED

S

1 R UNMATCHED

S

e.g.R = R = 10kꢃ, R = 0

S

S1

S2

2 R MATCHED

S

e.g.R = 10kꢃ, R = R = 5kꢃ

S

S1

S2

60

R

S1

R

S2

REGISTER

NOISE ONLY

40

10

50

10

100

1k

10k

100k

1M

100

500

1k

5k

10k

50k

FREQUENCY – Hz

R

– SOURCE RESISTANCE – ꢃ

S

Figure 4b. TBD

Figure 6. Peak-to-Peak Noise (0.1 Hz to 10 Hz) vs. Source

Resistance (Includes Resistor Noise)

Comments on Noise

The OP37 is a very low-noise monolithic op amp. The outstanding

input voltage noise characteristics of the OP37 are achieved

mainly by operating the input stage at a high quiescent current.

The input bias and offset currents, which would normally increase,

are held to reasonable values by the input bias current cancellation

circuit. The OP37A/E has I_Band I_OSof only 40 nA and 35 nA

respectively at 25°C. This is particularly important when the input

has a high source resistance. In addition, many audio amplifier

designers prefer to use direct coupling. The high I_B. TCV_OSof

previous designs have made direct coupling difficult, if not

impossible, to use.

At R_S< 1 kΩ key the OP37’s low voltage noise is maintained.

With R_S< 1 kΩ, total noise increases, but is dominated by the

resistor noise rather than current or voltage noise. It is only

beyond Rs of 20kil that current noise starts to dominate. The

argument can be made that current noise is not important for

applications with low to-moderate source resistances. The

crossover between the OP37 and OP07 and OP08 noise occurs

in the 15 kΩ to 40 kΩ region.

100

50

1

2

100

OP08/108

50

1

OP07

10

OP08/108

5534

1 R UNMATCHED

S

2

5

e.g.R = R = 10kꢃ, R = 0

S

S1 S2

OP07

10

2 R MATCHED

S

OP27/37

e.g.R = 10kꢃ, R = R = 5kꢃ

S1 S2

S

R

S1

1 R UNMATCHED

S

5

5534

R

S2

e.g.R = R = 10kꢃ, R = 0

REGISTER

S

S1

S2

2 R MATCHED

NOISE ONLY

S

1

50

e.g.R = 10kꢃ, R = R = 5kꢃ

S1 S2

S

OP27/37

100

500

1k

5k

10k

50k

R

S1

R

– SOURCE RESISTANCE – ꢃ

S

R

S2

REGISTER

NOISE ONLY

Figure 7. !0 Hz Noise vs. Source resistance (Inlcludes

Resistor Noise)

1

50

100

500

1k

5k

10k

50k

R

– SOURCE RESISTANCE – ꢃ

S

Figure 6 shows the 0.1 Hz to 10 Hz peak-to-peak noise. Here

the picture is less favorable; resistor noise is negligible, current

noise becomes important because it is inversely proportional to

the square-root of frequency. The crossover with the OP-07

occurs in the 3 kΩ to 5 kΩ range depending on whether bal-

anced or unbalanced source resistors are used (at 3 kΩ the I_B.

I_OSerror also can be three times the V_OSspec.).

Figure 5. Noise vs. Resistance (Including Resistor Noise

@ 1000 Hz)

Voltage noise is inversely proportional to the square-root of bias

current, but current noise is proportional to the square-root of

bias current. The OP37’s noise advantage disappears when high

source-resistors are used. Figures 5, 6, and 7 compare OP-37

observed total noise with the noise performance of other devices

in different circuit applications.

Therefore, for low-frequency applications, the OP07 is better

than the OP27/37 when Rs > 3 kΩ. The only exception is when

gain error is important. Figure 3 illustrates the 10 Hz noise. As

expected, the results are between the previous two figures.

Total noise = [( Voltage noise)2 + (current noise ϫ RS)2 +

(resistor noise_]1/2

For reference, typical source resistances of some signal sources

are listed in Table I.

Figure 5 shows noise versus source resistance at 1000 Hz. The

same plot applies to wideband noise. To use this plot, just multiply

the vertical scale by the square-root of the bandwidth.

–12–

REV. A

OP37

Table I. TBD

Source

by only 0.7 dB. With a 1 kΩ source, the circuit noise measures

63 dB below a 1 mV reference level, unweighted, in a 20 kHz

noise bandwidth.

Device

Impedance Comments

Gain (G) of the circuit at 1 kHz can be calculated by the expression:

Straln Gauge

<500 Ω

Typically used in low-frequency

applications.





R 

G = 0.101 1+



¹

Magnetic

Tapehead

<1500 Ω

Low I_Bvery important to reduce

set-magnetization problems when

direct coupling is used. OP37

I_Bcan be neglected.

R

₃

For the values shown, the gain is just under 100 (or 40 dB).

Lower gains can be accommodated by increasing R3, but gains

higher than 40 dB will show more equalization errors because of

the 8 MHz gain bandwidth of the OP27.

Magnetic

Phonograph

Cartridges

<1500 Ω

Similar need for low I_Bin direct

coupled applications. OP47 will not

introduce any self-magnetization

problem.

This circuit is capable of very low distortion over its entire range,

generally below 0.01% at levels up to 7 V rms. At 3 V output

levels, it will produce less than 0.03% total harmonic distortion

at frequencies up to 20 kHz.

Linear Variable <1500 Ω

Differential

Used in rugged servo-feedback

applications. Bandwidth of interest

is 400 Hz to 5 kHz.

Transformer

Capacitor C3 and resistor R4form a simple –6 dB per octave

rumble filter, with a corner at 22 Hz. As an option, the switch

selected shunt capacitor C4, a nonpolarized electrolytic, bypasses

the low-frequency rolloff. Placing the rumble filter’s high-pass

action after the preamp has the desirable result of discriminating

against the RIAA amplified low frequency noise components

and pickup-produced low-frequency disturbances.

Audio Applications

The following applications information has been abstracted from

a PMI article in the 12/20/80 issue of Electronic Design magazine

and updated.

C4 (2)

R5

220ꢂF

100kꢃ

+

A preamplifier for NAB tape playback is similar to an RIAA

phono preamp, though more gain is typically demanded, along

with equalization requiring a heavy low-frequency boost. The

circuit In Figure 4 can be readily modified for tape use, as

shown by Figure 5.

MOVING MAGNET

CARTRIDGE INPUT

LF ROLLOFF

OUT

C3

0.47ꢂF

IN

A1

OP27

Ca

150pF

Ra

R4

75kꢃ

C1

0.03ꢂF

47.5kꢃ

OUTPUT

R1

97.6kꢃ

–

0.47ꢂF

R2

7.87kꢃ

C2

0.01ꢂF

OP37

TAPE

HEAD

Ra

Ca

+

15kꢃ

R3

100ꢃ

R1

33kꢃ

R2

5kꢃ

G = 1kHz GAIN

0.01ꢂF

R1

R3

1 +

= 0.101 (

)

= 98.677 (39.9dB) AS SHOWN

100kꢃ

T1 = 3180ꢂs

T2 = 50ꢂs

Figure 8. TBD

Figure 9. TBD

Figure 8 is an example of a phono pre-amplifier circuit using the

OP27 for A1; R1-R2-C1-C2 form a very accurate RIAA net-

work with standard component values. The popular method to

accomplish RIAA phono equalization is to employ frequency-

dependent feedback around a high-quality gain block. Properly

chosen, an RC network can provide the three necessary time

constants of 3180 µs, 318 µs, and 75 µs.¹

While the tape-equalization requirement has a flat high frequency

gain above 3 kHz (t₂= 50 µs), the amplifier need not be stabilized

for unity gain. The decompensated OP37 provides a greater

bandwidth and slew rate. For many applications, the idealized

time constants shown may require trimming of R_Aand R2 to

optimize frequency response for non ideal tape head perfor-

mance and other factors.⁵

For initial equalization accuracy and stability, precision metal-

film resistors and film capacitors of polystyrene or polypropylene

are recommended since they have low voltage coefficients,

dissipation factors, and dielectric absorption.⁴(High-K ceramic

capacitors should be avoided here, though low-K ceramics—

such as NPO types, which have excellent dissipation factors,

and somewhat lower dielectric absorption—can be considered

for small values or where space is at a premium.)

The network values of the configuration yield a 50 dB gain at 1 kHz,

and the dc gain is greater than 70 dB. Thus, the worst-case out-

put offset is just over 500 mV. A single 0.47 µF output capacitor

can block this level without affecting the dynamic range.

The tape head can be coupled directly to the amplifier input,

since the worst-case bias current of 85 nA with a 400 mH, 100 µin.

head (such as the PRB2H7K) will not be troublesome.

The OP27 brings a 3.2 nV/√Hz voltage noise and 0.45 pA/√Hz

current noise to this circuit. To minimize noise from other sources,

R3 is set to a value of 100 Ω, which generates a voltage noise of

1.3 nV/√Hz. The noise increases the 3.2 nV/√Hz of the amplifier

One potential tape-head problem is presented by amplifier bias-

current transients which can magnetize a head. The OP27 and

REV. A

–13–

OP37

OP37 are free of bias-current transients upon power up or power

down. However, it is always advantageous to control the speed

of power supply rise and fall, to eliminate transients.

offset of this circuit will be very low, 1.7 mV or less, for a 40 dB

gain. The typical output blocking capacitor can be eliminated in

such cases, but is desirable for higher gains to eliminate switching

transients.

In addition, the dc resistance of the head should be carefully

controlled, and preferably below 1 kΩ. For this configuration,

the bias-current induced offset voltage can be greater than the

170 pV maximum offset if the head resistance is not sufficiently

controlled.

C2

1800pF

R1

121ꢃ

R2

1100ꢃ

A simple, but effective, fixed-gain transformerless microphone

preamp (Figure 10) amplifies differential signals from low imped-

ance microphones by 50 dB, and has an input impedance of 2 kΩ.

Because of the high working gain of the circuit, an OP37 helps

to preserve bandwidth, which will be 110 kHz. As the OP37 is a

decompensated device (minimum stable gain of 5), a dummy

resistor, R_P, may be necessary, if the microphone is to be

unplugged. Otherwise the 100% feedback from the open input

may cause the amplifier to oscillate.

A1

OUTPUT

T1*

OP27

150ꢃ

SOURCE

R3

100ꢃ

*T1 – JENSEN JE – 115K – E

JENSENTRANSFORMERS

10735 BURBANK BLVD.

N. HOLLYWOOD, CA 91601

Figure 11. TBD

C1

5ꢂF

R1

1kꢃ

R3

R6

Capacitor C2 and resistor R2 form a 2 µs time constant in this

circuit, as recommended for optimum transient response by

the transformer manufacturer. With C2 in use, A1 must have

unity-gain stability. For situations where the 2 µs time con-

stant is not necessary, C2 can be deleted, allowing the faster

OP37 to be employed.

316kꢃ

100ꢃ

–

LOW IMPEDANCE

MICROPHONE INPUT

(Z = 50ꢃTO 200ꢃ)

Rp

30kꢃ

R7

10kꢃ

OP37

OUTPUT

+

R2

R4

R3 R4

=

Some comment on noise is appropriate to understand the

capability of this circuit. A 150 Ω resistor and R1 and R2 gain

resistors connected to a noiseless amplifier will generate 220 nV

of noise in a 20 kHz bandwidth, or 73 dB below a 1 mV reference

level. Any practical amplifier can only approach this noise level;

it can never exceed it. With the OP27 and T1 specified, the

additional noise degradation will be close to 3.6 dB (or –69.5

referenced to 1 mV).

1kꢃ

316kꢃ

R1 R2

Figure 10. TBD

Common-mode input-noise rejection will depend upon the match

of the bridge-resistor ratios. Either close-tolerance (0.1%) types

should be used, or R4 should be trimmed for best CMRR. All

resistors should be metal-film types for best stability and low noise.

References

Noise performance of this circuit is limited more by the input

resistors R1 and R2 than by the op amp, as R1 and R2 each

generate a 4 nV√Hz noise, while the op amp generates a 3.2 nV√Hz

noise. The rms sum of these predominant noise sources will be

about 6 nV√Hz, equivalent to 0.9 µV in a 20 kHz noise bandwidth,

or nearly 61 dB below a l mV input signal. Measurements confirm

this predicted performance.

1. Lipshitz, S.P, “On RIAA Equalization Networks,” JAES, Vol. 27, June 1979,

p. 458-4S1.

2. Jung, W.G., IC Op Amp Cookbook, 2nd Ed., H.W. Sams and Company,

1980.

3. Jung, W.G., Audio /C Op Amp Applications, 2nd Ed., H.W. Sams and Com-

pany, 1978.

4. Jung, W.G., and Marsh, R.M., “Picking Capacitors.” Audio, February &

March, 1980.

5. Otala, M., “Feedback-Generated Phase Nonlinearity in Audio Amplifiers,”

London AES Convention, March 1980, preprint 197B.

6. Stout, D.F., and Kaufman, M., Handbook of Operational Amplifier Circuit

Design, New York, McGraw Hill, 1976.

For applications demanding appreciably lower noise, a high quality

microphone-transformer-coupled preamp (Figure 11) incorporates

the internally compensated. T1 is a JE-115K-E 150 Ω/15 kΩ

transformer which provides an optimum source resistance for

the OP27 device. The circuit has an overall gain of 40 dB, the

product of the transformer’s voltage setup and the op amp’s

voltage gain.

Gain may be trimmed to other levels, if desired, by adjusting R2

or R1. Because of the low offset voltage of the OP27, the output

–14–

REV. A

OP37

OUTLINE DIMENSIONS

Dimensions shown in inches and (mm).

8-Lead Hermetic DIP

(Z Suffix)

0.005 (0.13) 0.055 (1.4)

MIN

MAX

8

5

0.310 (7.87)

0.220 (5.59)

PIN 1

1

4

0.100 (2.54) BSC

0.405 (10.29) MAX

0.320 (8.13)

0.290 (7.37)

0.060 (1.52)

0.015 (0.38)

0.200 (5.08)

MAX

0.150

(3.81)

MIN

0.200 (5.08)

0.125 (3.18)

0.015 (0.38)

0.008 (0.20)

SEATING

PLANE

15°

0°

0.023 (0.58) 0.070 (1.78)

0.014 (0.36) 0.030 (0.76)

Epoxy Mini-Dip

(P Suffix)

0.430 (10.92)

0.348 (8.84)

8

5

0.280 (7.11)

0.240 (6.10)

1

4

0.325 (8.25)

0.300 (7.62)

PIN 1

0.100 (2.54)

BSC

0.060 (1.52)

0.015 (0.38)

0.210

(5.33)

MAX

0.195 (4.95)

0.115 (2.93)

0.130

(3.30)

MIN

0.160 (4.06)

0.115 (2.93)

0.015 (0.381)

0.008 (0.204)

0.022 (0.558) 0.070 (1.77) SEATING

0.014 (0.356) 0.045 (1.15)

PLANE

8-Lead SO

(S Suffix)

0.1968 (5.00)

0.1890 (4.80)

8

1

5

4

0.2440 (6.20)

0.2284 (5.80)

0.1574 (4.00)

0.1497 (3.80)

PIN 1

0.0196 (0.50)

0.0099 (0.25)

0.0500 (1.27)

BSC

ꢅ 45ꢁ

0.0688 (1.75)

0.0532 (1.35)

0.0098 (0.25)

0.0040 (0.10)

SEATING

PLANE

8ꢁ

0ꢁ

0.0500 (1.27)

0.0160 (0.41)

0.0192 (0.49)

0.0138 (0.35)

0.0098 (0.25)

0.0075 (0.19)

REV. A

–15–

OP37

Revision History

Location

Page

Data Sheet changed from REV. B to REV. C.

Edits to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1

Edits to ORDERING INFORMATION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1

Edits to PIN CONNECTIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1

Edits to ABSOLUTE MAXIMUM RATINGS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2

Edits to PACKAGE TYPE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2

Edits to ELECTRICAL CHARACTERISTICS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3

Edits to APPLICATIONS INFORMATION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8

–16–

REV. A

型号:	OP37EZ
生命周期：	Obsolete
IHS 制造商：	TEXAS INSTRUMENTS INC
零件包装代码：	DIP
包装说明：	CERAMIC, DIP-8
针数：	8
Reach Compliance Code：	unknown
ECCN代码：	EAR99
HTS代码：	8542.33.00.01
风险等级：	5.41
Is Samacsys：	N
放大器类型：	OPERATIONAL AMPLIFIER
最大平均偏置电流 (IIB)：	0.04 µA
标称共模抑制比：	128 dB
最大输入失调电压：	25 µV
JESD-30 代码：	R-GDIP-T8
长度：	9.905 mm
负供电电压上限：	-22 V
标称负供电电压 (Vsup)：	-15 V
功能数量：	1
端子数量：	8
最高工作温度：	85 °C
最低工作温度：	-25 °C
封装主体材料：	CERAMIC, GLASS-SEALED
封装代码：	DIP
封装形状：	RECTANGULAR
封装形式：	IN-LINE
认证状态：	Not Qualified
座面最大高度：	5.84 mm
标称压摆率：	11.9 V/us
供电电压上限：	22 V
标称供电电压 (Vsup)：	15 V
表面贴装：	NO
技术：	BIPOLAR
温度等级：	OTHER
端子形式：	THROUGH-HOLE
端子节距：	2.54 mm
端子位置：	DUAL
标称均一增益带宽：	63000 kHz
宽度：	7.62 mm
Base Number Matches：	1

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