OPA604AP各脚功能电路原理芯片引脚定义引脚图及功能IC贸易商-中国IC网-芯三七

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产品型号OPA604AP的概述

OPA604AP芯片概述 OPA604AP 是一款高性能的运算放大器，属于德州仪器（Texas Instruments）旗下的产品线。它主要设计用于高精度的信号处理应用，广泛应用于音频、视频以及数据采集等领域。OPA604AP具备极低的失真和噪声水平，以及宽广的带宽特性，使其成为各种精密模拟信号处理需求的重要选择。随着现代电子设备对信号处理精度和性能的不断提高，OPA604AP的研究和应用逐渐受到重视。 OPA604AP的详细参数 OPA604AP运算放大器提供了多项优异的性能指标，包括但不限于以下几个方面： 1. 带宽： - 增益带宽积（GBW）：约为 10MHz。这个参数决定了芯片在较高增益下的可用频率范围。 2. 增益特性： - 开环增益（AOL）：典型值为 100 V/V。 - 幅频特性：可支持较宽的带宽，适合高频信号处理。 3. 失真和噪声： - 总谐...

产品型号OPA604AP的Datasheet PDF文件预览

OPA604

FPO

FET-Input, Low Distortion

OPERATIONAL AMPLIFIER

FEATURES

APPLICATIONS

● LOW DISTORTION: 0.0003% at 1kHz

● PROFESSIONAL AUDIO EQUIPMENT

● LOW NOISE: 10nV/√Hz

● PCM DAC I/V CONVERTER

● SPECTRAL ANALYSIS EQUIPMENT

● ACTIVE FILTERS

● HIGH SLEW RATE: 25V/µs

● WIDE GAIN-BANDWIDTH: 20MHz

● UNITY-GAIN STABLE

● TRANSDUCER AMPLIFIER

● DATA ACQUISITION

● WIDE SUPPLY RANGE: V_S= ±4.5 to ±24V

● DRIVES 600Ω LOAD

● DUAL VERSION AVAILABLE (OPA2604)

(7)

V+

DESCRIPTION

The OPA604 is a FET-input operational amplifier

designed for enhanced AC performance. Very low

distortion, low noise and wide bandwidth provide

superior performance in high quality audio and other

applications requiring excellent dynamic performance.

(+)

(3)

(–)

New circuit techniques and special laser trimming of

dynamic circuit performance yield very low harmonic

distortion. The result is an op amp with exceptional

sound quality. The low-noise FET input of the OPA604

provides wide dynamic range, even with high source

impedance. Offset voltage is laser-trimmed to mini-

mize the need for interstage coupling capacitors.

Distortion

Rejection

Circuitry⁽¹⁾

(6)

V_O

Output

Stage⁽¹⁾

(2)

(5)

(1)

The OPA604 is available in 8-pin plastic mini-DIP

and SO-8 surface-mount packages, specified for the

–25°C to +85°C temperature range.

(4)

V–

NOTE: (1) Patents Granted: #5053718, 5019789

International Airport Industrial Park

•

Mailing Address: PO Box 11400

Cable: BBRCORP

•

Tucson, AZ 85734

•

Street Address: 6730 S. Tucson Blvd.

• Tucson, AZ 85706

Tel: (520) 746-1111 Twx: 910-952-1111

•

Telex: 066-6491

•

FAX: (520) 889-1510 Immediate Product Info: (800) 548-6132

•

PDS-1161C

Printed in U.S.A. May, 1995

SPECIFICATIONS

ELECTRICAL

T_A= +25°C, V_S= ±15V unless otherwise noted.

OPA604AP, AU

TYP

PARAMETER

CONDITION

MIN

MAX

UNITS

OFFSET VOLTAGE

Input Offset Voltage

Average Drift

±1

±8

100

±5

µV/°C

Power Supply Rejection

V_S= ±5 to ±24V

INPUT BIAS CURRENT⁽¹⁾

Input Bias Current

Input Offset Current

V_CM= 0V

±3

NOISE

Input Voltage Noise

Noise Density: f = 10Hz

f = 100Hz

1.5

nV/√Hz

µVp-p

f = 1kHz

f = 10kHz

Voltage Noise, BW = 20Hz to 20kHz

Input Bias Current Noise

Current Noise Density, f = 0.1Hz to 20kHz

fA/√Hz

INPUT VOLTAGE RANGE

Common-Mode Input Range

Common-Mode Rejection

±12

±13

100

V_CM= ±12V

INPUT IMPEDANCE

Differential

Common-Mode

10¹²|| 8

10¹²|| 10

Ω || pF

OPEN-LOOP GAIN

Open-Loop Voltage Gain

V_O= ±10V, R_L= 1kΩ

100

FREQUENCY RESPONSE

Gain-Bandwidth Product

Slew Rate

Settling Time: 0.01%

0.1%

G = 100

20Vp-p, R_L= 1kΩ

G = –1, 10V Step

1.5

MHz

V/µs

µs

Total Harmonic Distortion + Noise (THD+N)

G = 1, f = 1kHz

0.0003

V_O= 3.5Vrms, R_L= 1kΩ

OUTPUT

Voltage Output

Current Output

Short Circuit Current

Output Resistance, Open-Loop

R_L= 600Ω

V_O= ±12V

±11

±12

±35

±40

Ω

POWER SUPPLY

Specified Operating Voltage

Operating Voltage Range

Current

±15

±4.5

±24

±6

±5.3

TEMPERATURE RANGE

Specification

Storage

Thermal Resistance⁽²⁾, θ_JA

–25

–40

+85

+125

°C

°C/W

NOTES: (1) Typical performance, measured fully warmed-up. (2) Soldered to circuit board—see text.

The information provided herein is believed to be reliable; however, BURR-BROWN assumes no responsibility for inaccuracies or omissions. BURR-BROWN assumes

no responsibility for the use of this information, and all use of such information shall be entirely at the user’s own risk. Prices and specifications are subject to change

without notice. No patent rights or licenses to any of the circuits described herein are implied or granted to any third party. BURR-BROWN does not authorize or warrant

any BURR-BROWN product for use in life support devices and/or systems.

OPA604

PIN CONFIGURATION

ABSOLUTE MAXIMUM RATINGS

Power Supply Voltage ........................................................................ ±25V

Input Voltage ............................................................... (V–)–1V to (V+)+1V

Output Short Circuit to Ground ................................................ Continuous

Operating Temperature................................................... –40°C to +100°C

Storage Temperature ...................................................... –40°C to +125°C

Junction Temperature .................................................................... +150°C

Lead Temperature (soldering, 10s) AP .......................................... +300°C

Lead Temperature (soldering, 3s) AU ............................................ +260°C

Top View

DIP, SOIC

No Internal Connection

Offset Trim

–In

+V_S

+In

Output

Offset Trim

–V_S

ORDERING INFORMATION

MODEL

PACKAGE

TEMP. RANGE

OPA604AP

OPA604AU

8-Pin Plastic DIP

SO-8 Surface-Mount

–25°C to +85°C

ELECTROSTATIC

DISCHARGE SENSITIVITY

PACKAGE INFORMATION

PACKAGE DRAWING

NUMBER⁽¹⁾

Any integrated circuit can be damaged by ESD. Burr-Brown

recommends that all integrated circuits be handled with ap-

propriate precautions. Failure to observe proper handling and

installation procedures can cause damage.

MODEL

PACKAGE

OPA604AP

OPA604AU

8-Pin Plastic DIP

SO-8 Surface-Mount

006

182

NOTE: (1) For detailed drawing and dimension table, please see end of data

sheet, or Appendix D of Burr-Brown IC Data Book.

ESD damage can range from subtle performance degradation

to complete device failure. Precision integrated circuits may

be more susceptible to damage because very small parametric

changes could cause the device not to meet published speci-

fications.

OPA604

TYPICAL PERFORMANCE CURVES

T_A= +25°C, V_S= ±15V unless otherwise noted.

TOTAL HARMONIC DISTORTION + NOISE

vs FREQUENCY

TOTAL HARMONIC DISTORTION + NOISE

vs OUTPUT VOLTAGE

0.1

0.01

Measurement BW = 80kHz

See “Distortion Measure-

ments” for description of

test method.

See “Distortion Measurements”

for description of test method.

V_O

3.5Vrms

1kΩ

V_O

0.1

0.01

1kΩ

f = 1kHz

Measurement BW = 80kHz

G = 100V/V

G = 10V/V

0.001

0.0001

0.001

0.0001

G = 1V/V

100

Frequency (Hz)

10k 20k

0.1

100

Output Voltage (Vp-p)

INPUT VOLTAGE AND CURRENT NOISE

SPECTRAL DENSITY vs FREQUENCY

OPEN-LOOP GAIN/PHASE vs FREQUENCY

100

120

100

–45

–90

–135

–180

Voltage Noise

Current Noise

–20

100

10k

100k

100

10k

100k

10M

Frequency (Hz)

INPUT BIAS AND INPUT OFFSET CURRENT

vs TEMPERATURE

INPUT BIAS AND INPUT OFFSET CURRENT

vs INPUT COMMON-MODE VOLTAGE

100nA

10nA

1nA

100

10nA

1nA

100

1nA

100

1nA

100

Input

Bias Current

Input

Bias Current

Input

Offset Current

Input

Offset Current

0.1

–75

–50

–25

100

125

–15

–10

–5

Ambient Temperature (°C)

Common-Mode Voltage (V)

OPA604

TYPICAL PERFORMANCE CURVES (CONT)

T_A= +25°C, V_S= ±15V unless otherwise noted.

COMMON-MODE REJECTION

vs COMMON-MODE VOLTAGE

INPUT BIAS CURRENT

vs TIME FROM POWER TURN-ON

120

110

100

1nA

100

V_S= ±24VDC

V_S= ±15VDC

V_S= ±5VDC

–15

–10

–5

Common-Mode Voltage (V)

Time After Power Turn-On (min)

POWER SUPPLY AND COMMON-MODE

REJECTION vs FREQUENCY

A_OL, PSR, AND CMR vs SUPPLY VOLTAGE

120

110

100

120

100

120

+PSR

100

CMR

–PSR

PSR

A_OL

100

10k

100k

10M

Supply Voltage (±V_S)

Frequency (Hz)

GAIN-BANDWIDTH AND SLEW RATE

vs TEMPERATURE

GAIN-BANDWIDTH AND SLEW RATE

vs SUPPLY VOLTAGE

Slew Rate

Gain-Bandwidth

G = +100

Slew Rate

Gain-Bandwidth

G = +100

–75

–50

–25

100

125

Supply Voltage (±V_S)

Temperature (°C)

OPA604

TYPICAL PERFORMANCE CURVES (CONT)

T_A= +25°C, V_S= ±15V unless otherwise noted.

SETTLING TIME vs CLOSED-LOOP GAIN

MAXIMUM OUTPUT VOLTAGE SWING vs FREQUENCY

V_S= ±15V

V_O= 10V Step

R_L= 1kΩ

C_L= 50pF

0.01%

0.1%

–1

–10

–100

–1000

10k

100k

Frequency (Hz)

10M

Closed-Loop Gain (V/V)

LARGE-SIGNAL TRANSIENT RESPONSE

SUPPLY CURRENT vs TEMPERATURE

+10

V_S= ±15VDC

V_S= ±24VDC

V_S= ±5VDC

FPO

Bleed to edge

–10

–75

–50

–25

100

125

Ambient Temperature (°C)

Time (µs)

SHORT-CIRCUIT CURRENT vs TEMPERATURE

I_SC+and I_SC–

SMALL-SIGNAL TRANSIENT RESPONSE

+100

–100

–75

–50

–25

100

125

1µs

2µs

Ambient Temperature (°C)

Time (µs)

OPA604

TYPICAL PERFORMANCE CURVES (CONT)

T_A= +25°C, V_S= ±15V unless otherwise noted.

MAXIMUM POWER DISSIPATION vs TEMPERATURE

POWER DISSIPATION vs SUPPLY VOLTAGE

1.4

1.2

1.0

0.8

0.6

0.4

0.2

0.5

0.45

0.40

0.35

0.30

0.25

0.20

0.15

0.10

0.05

θ_J-A= 90°C/W

Soldered to

Circuit Board

(see text)

Worst case sine

wave R_L= 600Ω

Typical high-level

music R_L= 600Ω

Maximum

Specified Operating

Temperature

85°C

No signal

or no load

100

125

150

Ambient Temperature (°C)

Supply Voltage, ±V_S(V)

Op amp distortion can be considered an internal error source

which can be referred to the input. Figure 2 shows a circuit

which causes the op amp distortion to be 101 times greater

than normally produced by the op amp. The addition of R₃

to the otherwise standard noninverting amplifier configura-

tion alters the feedback factor or noise gain of the circuit.

The closed-loop gain is unchanged, but the feedback avail-

able for error correction is reduced by a factor of 101. This

extends the measurement limit, including the effects of the

signal-source purity, by a factor of 101. Note that the input

signal and load applied to the op amp are the same as with

conventional feedback without R₃.

APPLICATIONS INFORMATION

OFFSET VOLTAGE ADJUSTMENT

The OPA604 offset voltage is laser-trimmed and will require

no further trim for most applications. As with most amplifi-

ers, externally trimming the remaining offset can change

drift performance by about 0.3µV/°C for each 100µV of

adjusted offset. The OPA604 can replace many other ampli-

fiers by leaving the external null circuit unconnected.

The OPA604 is unity-gain stable, making it easy to use in a

wide range of circuitry. Applications with noisy or high

impedance power supply lines may require decoupling ca-

pacitors close to the device pins. In most cases, a 1µF

tantalum capacitor at each power supply pin is adequate.

Validity of this technique can be verified by duplicating

measurements at high gain and/or high frequency where the

distortion is within the measurement capability of the test

equipment. Measurements for this data sheet were made

with the Audio Precision System One which greatly simpli-

fies such repetitive measurements. The measurement tech-

nique can, however, be performed with manual distortion

measurement instruments.

+V_CC

OPA604

CAPACITIVE LOADS

±50mV Typical

Trim Range

The dynamic characteristics of the OPA604 have been

optimized for commonly encountered gains, loads and oper-

ating conditions. The combination of low closed-loop gain

and capacitive load will decrease the phase margin and may

lead to gain peaking or oscillations. Load capacitance reacts

with the op amp’s open-loop output resistance to form an

additional pole in the feedback loop. Figure 3 shows various

circuits which preserve phase margin with capacitive load.

Request Application Bulletin AB-028 for details of analysis

techniques and applications circuits.

(1)

NOTE: (1) 50kΩ to 1MΩ

Trim Potentiometer

–V_CC

(100kΩ Recommended)

FIGURE 1. Offset Voltage Trim.

DISTORTION MEASUREMENTS

The distortion produced by the OPA604 is below the mea-

surement limit of virtually all commercially available equip-

ment. A special test circuit, however, can be used to extend

the measurement capabilities.

For the unity-gain buffer, Figure 3a, stability is preserved by

adding a phase-lead network, R_Cand C_C. Voltage drop

OPA604

across R_Cwill reduce output voltage swing with heavy

loads. An alternate circuit, Figure 3b, does not limit the

output with low load impedance. It provides a small amount

of positive feedback to reduce the net feedback factor. Input

impedance of this circuit falls at high frequency as op amp

gain rolloff reduces the bootstrap action on the compensa-

tion network.

will dominate. At a few thousand ohms source impedance

and above, the OPA604 will generally provide lower noise.

POWER DISSIPATION

The OPA604 is capable of driving a 600Ω load with power

supply voltages up to ±24V. Internal power dissipation is

increased when operating at high power supply voltage. The

typical performance curve, Power Dissipation vs Power

Supply Voltage, shows quiescent dissipation (no signal or

no load) as well as dissipation with a worst case continuous

sine wave. Continuous high-level music signals typically

produce dissipation significantly less than worst case sine

waves.

Figures 3c and 3d show compensation techniques for

noninverting amplifiers. Like the follower circuits, the cir-

cuit in Figure 3d eliminates voltage drop due to load current,

but at the penalty of somewhat reduced input impedance at

high frequency.

Figures 3e and 3f show input lead compensation networks

for inverting and difference amplifier configurations.

Copper leadframe construction used in the OPA604 im-

proves heat dissipation compared to conventional plastic

packages. To achieve best heat dissipation, solder the device

directly to the circuit board and use wide circuit board

traces.

NOISE PERFORMANCE

Op amp noise is described by two parameters—noise volt-

age and noise current. The voltage noise determines the

noise performance with low source impedance. Low noise

bipolar-input op amps such as the OPA27 and OPA37

provide very low voltage noise. But if source impedance is

greater than a few thousand ohms, the current noise of

bipolar-input op amps react with the source impedance and

OUTPUT CURRENT LIMIT

Output current is limited by internal circuitry to approxi-

mately ±40mA at 25°C. The limit current decreases with

increasing temperature as shown in the typical curves.

R₁

R₂

SIG. DIST.

R₁

R₂

R₃

GAIN GAIN

101

∞

5kΩ

50Ω

101 500Ω 5kΩ 500Ω

R₃

OPA604

V_O= 10Vp-p

(3.5Vrms)

100

101

50Ω

5kΩ

∞

Generator

Output

Analyzer

Input

Audio Precision

System One

Analyzer⁽¹⁾

IBM PC

Compatible

R_L

1kΩ

NOTE: (1) Measurement BW = 80kHz

FIGURE 2. Distortion Test Circuit.

OPA604

(a)

(b)

C_C

820pF

R_C

e_o

OPA604

e_o

OPA604

C_C

0.47µF

e_i

750Ω

C_L

5000pF

C_L

5000pF

R₂

R_C

10Ω

e_i

C_C

120 X 10^–12C_L

2kΩ

R₂

R_C

C_C

4C_LX 10¹⁰– 1

C_LX 10³

R_C

(c)

(d)

R₁

R₂

R₁

2kΩ

R₂

10kΩ

2kΩ

C_C

R_C

20Ω

24pF

C_C

0.22µF

R_C

e_o

OPA604

e_i

25Ω

e_i

C_L

5000pF

C_L

5000pF

R₂

R_C

C_C

C_L

2C_LX 10¹⁰– (1 + R₂/R₁)

R₂

C_LX 10³

R_C

(e)

(f)

R₂

R₁

2kΩ

R₂

e₁

2kΩ

R₁

R_C

e_i

20Ω

2kΩ

e_o

OPA604

C_C

0.22µF

R_C

20Ω

C_L

5000pF

C_L

5000pF

R₃

2kΩ

R_C

R₄

C_C

0.22µF

e₂

2kΩ

R₂

R_C

C_C

2C_LX 10¹⁰– (1 + R₂/R₁)

R₂

2C_LX 10¹⁰– (1 + R₂/R₁)

C_LX 10³

R_C

C_LX 10³

R_C

C_C

NOTE: Design equations and component values are approximate. User adjustment is required for optimum performance.

FIGURE 3. Driving Large Capacitive Loads.

OPA604

R₄

22kΩ

C₃

100pF

R₁

R₂

R₃

V_IN

OPA604

V_O

2.7kΩ

22kΩ

10kΩ

C₁

3000pF

C₂

2000pF

f_p= 20kHz

FIGURE 4. Three-Pole Low-Pass Filter.

R₁

R₅

OPA604

V_O

V_IN

6.04kΩ

2kΩ

R₂

C₃

1000pF

4.02kΩ

R₂

Low-pass

3-pole Butterworth

f_–3dB= 40kHz

4.02kΩ

OPA2604

C₁

1000pF

R₄

5.36kΩ

See Application Bulletin AB-026

for information on GIC filters.

C₂

1000pF

FIGURE 5. Three-Pole Generalized Immittance Converter (GIC) Low-Pass Filter.

10kΩ

7.87kΩ

OPA2604

–

V_IN

100pF

OPA604

V_O

G = 1

7.87kΩ

100kHz Input Filter

OPA2604

10kΩ

FIGURE 6. Differential Amplifier with Low-Pass Filter.

OPA604

C_OUT

100Ω

10kΩ

NOTE: (1) C₁

≈

2π R_ff_c

R_F= Internal feedback resistance = 1.5kΩ

G = 101

(40dB)

f_C= Crossover frequency = 8MHz

OPA604

(1)

C₁

Piezoelectric

Transducer

PCM63

20-bit

D/A

Converter

1MΩ⁽¹⁾

OPA604

V_O= ±3Vp

To low-pass

filter.

NOTE: (1) Provides input

bias current return path.

FIGURE 7. High Impedance Amplifier.

FIGURE 8. Digital Audio DAC I-V Amplifier.

OPA604

A₂

I₂

R₄

51Ω

R₃

OPA604

51Ω

A₁

I_L= I₁+ I₂

I₁

V_IN

R₂

V_OUT

Load

R₁

V_OUT= V_IN(1+R₂/R₁)

FIGURE 9. Using Two OPA604 Op Amps to Double the Output Current to a Load.

OPA604

SOUND QUALITY

The following discussion is provided, recognizing that

I₂

I₁

not all measured performance behavior explains or

correlates with listening tests by audio experts. The

design of the OPA604 included consideration of both

objective performance measurements, as well as an

awareness of widely held theory on the success and

failure of previous op amp designs.

R₆

800µA

500Ω

200µA

R₁

R₂

R₅

R₇

75Ω

500Ω

4kΩ

(+)

J₃

J₄

J₁

J₂

(–)

Distortion

Output

Stage

Rejection

Circuitry

J₅

SOUND QUALITY

The sound quality of an op amp is often the crucial

selection criteria—even when a data sheet claims ex-

ceptional distortion performance. By its nature, sound

quality is subjective. Furthermore, results of listening

tests can vary depending on application and circuit

configuration. Even experienced listeners in controlled

tests often reach different conclusions.

Q₂

R₁₀

10kΩ

Q₃

Q₁

Q₄

R₁₁

10kΩ

R₃

R₄

R₈

R₉

3kΩ

1kΩ

3kΩ

Many audio experts believe that the sound quality of a

high performance FET op amp is superior to that of

bipolar op amps. A possible reason for this is that

bipolar designs generate greater odd-order harmonics

than FETs. To the human ear, odd-order harmonics

have long been identified as sounding more unpleasant

than even-order harmonics. FETs, like vacuum tubes,

have a square-law I-V transfer function which is more

linear than the exponential transfer function of a bipo-

lar transistor. As a direct result of this square-law

characteristic, FETs produce predominantly even-or-

der harmonics. Figure 10 shows the transfer function

of a bipolar transistor and FET. Fourier transformation

of both transfer functions reveals the lower odd-order

harmonics of the FET amplifier stage.

THE OPA604 DESIGN

The OPA604 uses FETs throughout the signal path,

including the input stage, input-stage load, and the

important phase-splitting section of the output stage.

Bipolar transistors are used where their attributes,

such as current capability are important, and where

their transfer characteristics have minimal impact.

The topology consists of a single folded-cascode gain

stage followed by a unity-gain output stage. Differen-

tial input transistors J₁and J₂are special large-geom-

etry, P-channel JFETs. Input stage current is a rela-

tively high 800µA, providing high transconductance

and reducing voltage noise. Laser trimming of stage

currents and careful attention to symmetry yields a

nearly symmetrical slew rate of ±25V/µs.

V_BE= 1kHz + DC Bias

FFT

I_C

V_O

I_C

(mA)

log

(V_O)

V_BE

The JFET input stage holds input bias current to

approximately 50pA or roughly 3000 times lower

than common bipolar-input audio op amps. This dra-

matically reduces noise with high-impedance circuitry.

f_O

2f_O3f_O4f_O5f_O

0.65

The drains of J₁and J₂are cascoded by Q₁and Q₂,

driving the input stage loads, FETs J₃and J₄. Distor-

tion reduction circuitry (patented) linearizes the open-

loop response and increases voltage gain. The 20MHz

bandwidth of the OPA604 further reduces distortion

through the user-connected feedback loop.

V_BE(V)

Frequency (kHz)

V_GS= 1kHz + DC Bias

FFT

V_GS

–I_D

(mA)

log

(V_O)

V_O

I_D

The output stage consists of a JFET phase-splitter

loaded into high speed all-NPN output drivers. Output

transistors are biased by a special circuit to prevent

cutoff, even with full output swing into 600Ω loads.

f_O

2f_O3f_O4f_O5f_O

V_GS(V)

Frequency (kHz)

FIGURE 10. I-V and Spectral Response of NPN and

JFET.

OPA604

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OPA604AP产品参数

型号:	OPA604AP
Brand Name：	Texas Instruments
是否无铅：	不含铅
是否Rohs认证：	符合
生命周期：	Active
IHS 制造商：	TEXAS INSTRUMENTS INC
零件包装代码：	DIP
包装说明：	DIP, DIP8,.3
针数：	8
Reach Compliance Code：	compliant
ECCN代码：	EAR99
HTS代码：	8542.33.00.01
Factory Lead Time：	6 weeks
风险等级：	1.41
放大器类型：	OPERATIONAL AMPLIFIER
架构：	VOLTAGE-FEEDBACK
最大平均偏置电流 (IIB)：	0.0002 µA
最小共模抑制比：	80 dB
标称共模抑制比：	100 dB
频率补偿：	YES
最大输入失调电压：	5000 µV
JESD-30 代码：	R-PDIP-T8
JESD-609代码：	e4
长度：	9.81 mm
低-偏置：	YES
低-失调：	NO
微功率：	NO
负供电电压上限：	-25 V
标称负供电电压 (Vsup)：	-15 V
功能数量：	1
端子数量：	8
最高工作温度：	85 °C
最低工作温度：	-25 °C
封装主体材料：	PLASTIC/EPOXY
封装代码：	DIP
封装等效代码：	DIP8,.3
封装形状：	RECTANGULAR
封装形式：	IN-LINE
包装方法：	TUBE
峰值回流温度（摄氏度）：	NOT SPECIFIED
功率：	NO
电源：	+-15 V
可编程功率：	NO
认证状态：	Not Qualified
座面最大高度：	5.08 mm
最小摆率：	15 V/us
标称压摆率：	25 V/us
子类别：	Operational Amplifier
最大压摆率：	7 mA
供电电压上限：	25 V
标称供电电压 (Vsup)：	15 V
表面贴装：	NO
技术：	FET
温度等级：	OTHER
端子面层：	Nickel/Palladium/Gold (Ni/Pd/Au)
端子形式：	THROUGH-HOLE
端子节距：	2.54 mm
端子位置：	DUAL
处于峰值回流温度下的最长时间：	NOT SPECIFIED
标称均一增益带宽：	20000 kHz
最小电压增益：	10000
宽带：	NO
宽度：	6.35 mm
Base Number Matches：	1

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