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产品型号SP6125EK1-L的Datasheet PDF文件预览

SP6125  
High-Voltage, Step Down Controller in TSOT6  
FEATURES  
Wide 4.5V – 29V Input Voltage Range  
Internal Compensation  
GND  
5
LX  
6
FB  
4
Built-in High Current PMOS Driver  
Adjustable Overcurrent Protection  
Internal soft-start  
SP6125  
300kHz Constant Frequency Operation  
0.6V Reference Voltage  
6 PinTSOT  
1% output setpoint accuracy  
Lead Free, RoHS Compliant Package:  
Small 6 pin TSOT  
1
VIN  
2
3
VDR  
GATE  
DESCRIPTION  
The SP6125 is a PWM controlled step down (buck) voltage mode regulator with VIN feedforward and  
internal Type-II compensation. It operates from 4.5V to 29V, making is suitable for 5V, 12V, and 24V  
applications. By using a PMOS driver, this device is capable of operating at 100% duty cycle. The  
high side driver is designed to drive the gate 5V below VIN. The programmable overcurrent  
protection is based on high-side MOSFET’s ON resistance sensing and allows setting the  
overcurrent protection value up to 300mV threshold (measured from VIN-LX). The SP6125 is  
available in a space-saving 6-pin TSOT package making it the smallest controller available capable  
of operating from 24VDC supplies.  
TYPICAL APPLICATION CIRCUIT  
VIN  
C1  
4.7uF  
C2  
4.7uF  
24V  
Q1  
2
FDS4685  
1
3
Gate  
LX  
GND  
VOUT  
Vin  
L1, IHLP-2525CZ  
8.2uH, 68mOhm, 4A  
Rs 2k  
6
C6  
0.1uF  
C4  
22uF  
C5  
3.3V  
0-3A  
SP6125  
Ds  
RZ  
22uF  
MBRA340T3G 2K  
R1  
300k, 1%  
VDR  
CZ  
4
47pF  
GND  
VFB  
GND  
5
R2  
66.5k, 1%  
D1 1N4148  
SHDN  
High=Off  
Jan28-08 RevG  
SP6125: TSOT-6 PFET Buck Controller  
2007 Exar Corporation  
1
ABSOLUTE MAXIMUM RATINGS  
Input Voltage……................................................-0.3V to 30V  
Lx………………………………………..………….…-2V to 30V  
FB……………....................................................-0.3V to 5.5V  
Storage Temperature..……..…………...……-65 °C to 150 °C  
Junction Temperature.....................................-40°C to 125°C  
Lead Temperature (Soldering, 1…0 sec)….…………..300 °C  
ESD Rating……….…….…1kV LX, 2kV all other nodes, HBM  
These are stress ratings only, and functional  
operation of the device at these ratings or any other  
above those indicated in the operation sections of the  
specifications below is not implied. Exposure to  
absolute maximum rating conditions for extended  
periods of time may affect reliability.  
ELECTRICAL SPECIFICATIONS  
Specifications are for TAMB=TJ=25°C, and those denoted by apply over the full operating range, -40°C< Tj <125°C. Unless  
otherwise specified: VIN =4.5V to 29V, CIN = 4.7µF.  
PARAMETER  
UVLO Turn-On Threshold  
UVLO Turn-Off Threshold  
UVLO Hysterisis  
MIN  
4.2  
TYP MAX UNITS  
CONDITIONS  
0°C< Tj <125°C  
4.35  
4.2  
4.5  
4.4  
V
V
V
4.0  
0°C< Tj <125°C  
0.2  
Operating Input Voltage  
Range  
Operating Input Voltage  
Range  
4.5  
7
29  
29  
V
V
0°C< Tj <125°C  
Operating VCC Current  
0.3  
0.5  
0.5  
3
1
2
mA  
%
VFB=1.2V  
Reference Voltage Accuracy  
Reference Voltage Accuracy  
%
Reference Voltage  
Reference Voltage  
0.594  
0.588  
255  
0.6  
0.6  
300  
0.606  
0.612  
345  
V
V
Switching Frequency  
Peak-to-peak ramp Modulator  
kHz  
V
VIN/5  
Minimum ON-Pulse Duration  
40  
100  
0
ns  
Minimum Duty Cycle  
Maximum Duty Cycle  
Gate Driver Turn-Off  
Resistance  
Gate Driver Pull-Down  
Resistance  
%
%
100  
4.5  
Internal resistor between GATE and  
50  
4
60  
8
k  
V
IN  
V
IN=12V, VFB=0.5V, Measure  
resistance between GATE and VDR  
VIN=12V, VFB=0.7V, Measure  
resistance between GATE and VIN  
Measure VIN – VDR, VIN>7V  
Gate Driver Pull-up  
Resistance  
3
6
V
IN - VDR voltage difference  
5.5  
V
Overcurrent Threshold  
270  
25  
300  
330  
35  
mV  
Measure VIN - LX  
VLX = VIN  
LX pin Input Current  
OFF interval during hiccup  
30  
200  
uA  
ms  
VFB=0.58V, measure between  
Soft start time  
3
5
9
ms  
V
IN=4.5V and first GATE pulse  
SHDN Threshold  
0.9  
1.0  
1.1  
V
Apply voltage to FB  
SHDN Threshold Hysteresis  
100  
mV  
Jan28-08 RevG  
SP6125: TSOT-6 PFET Buck Controller  
2007 Exar Corporation  
2
PIN DESCRIPTION  
PIN  
NAME  
PIN #  
DESCRIPTION  
Input power supply for the controller. Place input decoupling capacitor as close  
as possible to this pin.  
1
2
VIN  
GATE  
VDR  
Connect to the gate terminal of the external P-channel MOSFET.  
Power supply for the internal driver. This voltage is internally regulated to  
about 5V below VIN. Place a 0.1uF decoupling capacitor between VDR and  
Vin as close as possible to the IC.  
3
Regulator feedback input. Connect to a resistive voltage-divider network to set  
the output voltage. This pin can be also used for ON/OFF control. If this pin is  
pulled above 1V the P-channel driver is disabled and controller resets internal  
soft start circuit.  
4
5
FB  
GND  
Ground pin.  
This pin is used as a current limit input for the internal current limit comparator.  
Connect to the drain pin of the external MOSFET through an optional resistor.  
Internal threshold is pre-set to 300mV nominal and can be decreased by  
6
LX  
changing the external resistor based on the following formula: VTRSHLD  
300mV – 30uA * R  
=
BLOCK DIAGRAM  
VIN  
5V  
VDR  
Oscillator  
Vin - 5V LDO  
VIN  
5V Internal LDO  
I = k x VIN  
FAULT  
PWM Latch  
Reset Dominant  
VREF  
GATE  
S
R
+
-
FB  
+
-
PWM Comparator  
FAULT  
Error Amplifier  
VDR  
FAULT  
ENBL  
LX  
-
+
UVLO  
FAULT  
Register  
Overcurrent  
Comparator  
30uA  
200ms delay  
S
4-Bit counter  
POR  
VIN - 0.3V  
GND  
R
R
+
-
1V  
Set Dominant  
Jan28-08 RevG  
SP6125: TSOT-6 PFET Buck Controller  
2007 Exar Corporation  
3
General Overview  
Type-II internal compensation is sufficient if the  
following condition is met:  
The SP6125 is a fixed frequency, Voltage-  
mode, non-synchronous PWM controller  
optimized for minimum component, small form  
factor and cost effectiveness. It has been  
designed for single-supply operation ranging  
from 4.5V to 29V. SP6125 has Type-II internal  
compensation for use with Electrolytic or  
Tantalum output capacitors. For ceramic  
capacitors Type-III compensation can be  
implemented by simply adding an R and C  
between output and Feedback. A precision  
0.6V reference, present on the positive terminal  
of the Error Amplifier, permits programming of  
the output voltage down to 0.6V via the FB pin.  
The output of the Error Amplifier is internally  
compared to a feed-forward (VIN/5 peak-to-  
peak) ramp and generates the PWM control.  
Timing is governed by an internal oscillator that  
sets the PWM frequency at 300kHz.  
fESRZERO < fDBPOLE ………………. (1)  
where:  
1
fESRZERO  
=
……….. (2)  
………… (3)  
2.  
π
.RESR .COUT  
1
fDBPOLE  
=
2.  
π . L COUT  
L C  
CZ =  
……………………….. (4)  
1.3× R  
1
SP6125 contains useful protection features.  
Overcurrent protection is based on high-side  
MOSFET’s RDS(ON) and is programmable via a  
resistor placed at LX node. Under-Voltage  
Lock-Out (UVLO) ensures that the controller  
starts functioning only when sufficient voltage  
exists for powering IC’s internal circuitry.  
Creating a Type-III compensation Network  
The above condition requires the ESR zero to  
be at a lower frequency than the double-pole  
from the LC filter. If this condition is not met,  
Type-III compensation should be used and can  
be accomplished by placing a series RC  
combination in parallel with R1 as shown  
below. The value of CZ can be calculated as  
follows and RZ selected from table 1.  
SP6125 Loop Compensation  
The SP6125 includes Type-II internal  
compensation components for loop compen-  
sation. External compensation components are  
not required for systems with tantalum or  
aluminum electrolytic output capacitors with  
sufficiently high ESR. Use the condition below  
as a guideline to determine whether or not the  
internal compensation is sufficient for your  
design.  
fESRZERO÷fDBPOLE  
RZ  
1X  
2X  
3X  
5X  
50K  
40K  
30K  
10K  
2K  
>= 10X  
Table1- Selection of RZ  
Jan28-08 RevG  
SP6125: TSOT-6 PFET Buck Controller  
2007 Exar Corporation  
4
General Overview  
Vout  
SP6125  
CP1 2pF  
RZ  
CZ  
CZ2 130pF  
RZ2 200k  
R1  
300k, 1%  
VFB  
-
+
Vref=0.6V  
R2  
Error Amplifier  
Figure 1- RZ and CZ in conjunction with internal  
compensation components form a Type-III compensation  
Loop Compensation Example 1- A converter  
utilizing a SP6125 has a 8.2uH inductor and  
two 22uF/5mceramic capacitor.  
Determine whether Type-III compensation is  
needed.  
response of the circuit, seen in figure 2,  
validates the above procedure.  
Loop Compensation Example 2- A converter  
utilizing a SP6125 has a 8.2uH inductor and  
a
150uF, 82mAluminum Electrolytic  
capacitor. Determine whether Type-III  
compensation is needed.  
From equation (2) fESRZERO = 1.45MHz. From  
equation (3) fDBPOLE = 8.4kHz. Since the  
condition specified in (1) is not met, Type-III  
compensation has to be used by adding  
external components RZ and CZ. Using  
equation (4) CZ is calculated 48.7pF (use 47  
pF). Following the guideline given in table 1,  
a 2kRZ should be used.  
From equation (2) fESRZERO = 13kHz. From  
equation (3) fDBPOLE = 4.5kHz. Since the  
condition specified in (1) is not met, Type-III  
compensation has to be used by adding  
external components RZ and CZ. Using  
equation (4) CZ is calculated 89.9pF (use  
The steps followed in example 1 were used  
to compensate the typical application circuit  
shown on page 1. Satisfactory frequency  
100pF). Since fESRZERO ÷ fDBPOLE is  
approximately 3, RZ has to be set at 30k.  
Figure 2- Satisfactory frequency response of typical application circuit shown on page 1.  
Crossover frequency fc is about 35kHz with a corresponding phase margin of 60 degrees. The  
two sets of curves, which are essentially identical, correspond to load current of 1A and 2.5A.  
Jan28-08 RevG  
SP6125: TSOT-6 PFET Buck Controller  
2007 Exar Corporation  
5
General Overview  
Overcurrent protection  
Using the ON/OFF Function  
Vin  
The Feedback pin serves a dual role of  
ON/OFF control. The MOSFET driver is  
disabled when a voltage greater than 1V is  
applied at the FB pin. Maximum voltage rating  
of this pin is 5.5V. The controlling signal should  
be applied through a small signal diode as  
shown on page 1. Please note that an optional  
10kbleeding resistor across the output helps  
keep the output capacitor discharged under no  
load condition.  
SP6125  
Gate  
LX  
Q1  
Over-Current Comparator  
Rs  
-
+
Ds  
30uA  
Vin - 0.3V  
Programming the Output Voltage  
To program the output voltage, calculate R2  
using the following equation:  
Figure 3- Overcurrent protection circuit  
R1  
R2 =  
The overcurrent protection circuit functions by  
monitoring the voltage across the high-side FET  
Q1. When this voltage exceeds 0.3V, the  
overcurrent comparator triggers and the  
controller enters hiccup mode. For example if  
Q1 has Rds(on)=0.1, then the overcurrent will  
trigger at I = 0.3V/0.1=3A. To program a lower  
overcurrent use a resistor Rs as shown in figure  
1. Calculate Rs from:  
Vout  
Vref  
1  
Where:  
Vref=0.6 is the reference voltage of the SP6125  
R1=200kis a fixed-value resistor that, in  
addition to being a voltage divider, it is part of  
the compensation network. In order to simplify  
compensation calculations, R1 is fixed at  
200k.  
0.3 −  
(
1.15× Iout × Rds(on)  
)
Rs =  
……… (5)  
30uA  
The overcurrent circuit triggers at peak current  
through Q1 which is usually about 15% higher  
than average output current. Hence the  
multiplier 1.15 is used in (5).  
Soft Start  
Soft Start is preset internally to 5ms (nominal).  
Internal Soft Start eliminates the need for the  
external capacitor CSS that is commonly used  
to program this function.  
Example: A switching MOSFET used with  
SP6125 has Rds(on) of 0.1. Program the over-  
current circuit so that maximum output is 2A.  
MOSFET Gate Drive  
P-channel drive is derived through an internal  
regulator that generates VIN-5V. This pin (VDR)  
has to be connected to VIN with a 0.1uF  
decoupling capacitor. The gate drive circuit  
swings between VIN and VIN-5 and employs  
powerful drivers for efficient switching of the P-  
channel MOSFET.  
0.3 −  
(
1.15× 2A× 0.1Ohm  
)
Rs =  
30uA  
Rs = 2333Ω  
Using the above equation there is good  
agreement between calculated and test results  
for Rs in the range of 0.5kto 3k. For Rs  
larger than 3ktest results are lower than those  
predicted by (5), due to circuit parasitics.  
Therefore maximum value of Rs should be  
limited to 3k.  
Jan28-08 RevG  
SP6125: TSOT-6 PFET Buck Controller  
2007 Exar Corporation  
6
General Overview  
Power MOSFET Selection  
where:  
Vf is diode forward voltage at IOUT  
Select the Power MOSFET for Voltage rating  
BVDSS, On resistance RDS(ON), and thermal  
resistance Rthja. BVDSS should be about twice  
as high as VIN in order to guard against  
switching transients. Recommended MOSFET  
voltage rating for VIN of 5V, 12V and 24V is  
12V, 30V and 40V respectively. RDS(ON), must  
be selected such that when operating at peak  
Schottky’s AC losses due to its switching  
capacitance are negligible.  
Inductor Selection  
Select the Inductor for inductance L and  
saturation current Isat. Select an inductor with  
Isat higher than the programmed overcurrent.  
Calculate inductance from:  
current  
and  
junction  
temperature  
the  
Overcurrent threshold of the SP6125 is not  
exceeded. Allowing 50% for temperature  
coefficient of RDS(ON) and 15% for inductor  
current ripple, the following expression can be  
used:  
   
Vout  
Vin  
1
1
   
L =  
(Vin Vout  
)
×
×
×
   
   
f
Irip  
where:  
300mV  
RDS(ON) ≤  
1.5×1.15× Iout  
V
V
IN is converter input voltage  
OUT is converter output voltage  
Within this constraint, selecting MOSFETs with  
lower RDS(ON) will reduce conduction losses at  
the expense of increased switching losses. As  
a rule of thumb select the highest RDS(ON)  
MOSFET that meets the above criteria.  
Switching losses can be assumed to roughly  
equal the conduction losses. A simplified  
expression for conduction losses is given by:  
f is switching frequency  
RIP is inductor peak-to-peak current ripple  
(nominally set to 30% of IOUT  
I
)
Keep in mind that a higher IRIP results in a  
smaller inductor which has the advantages of  
small size, low DC equivalent resistance DCR,  
high saturation current Isat and allows the use  
of a lower output capacitance to meet a given  
step load transient. A higher Irip, however,  
increases the output voltage ripple and  
increases the current at which converter enters  
Discontinuous Conduction Mode. The output  
current at which converter enters DCM is ½ of  
Vout  
Pcond = Iout × RDS(ON)×  
Vin  
MOSFET’s junction temperature can be  
estimated from:  
I
RIP. Note that a negative current step load that  
T =  
(
2× Pc× Rthja + Tambient  
)
drives the converter into DCM will result in a  
large output voltage transient. Therefore the  
lowest current for a step load should be larger  
Schottky Rectifier selection  
than ½ of IRIP  
.
Select the Schottky for Voltage rating VR,  
Forward voltage Vf, and thermal resistance  
Rthja. Voltage rating should be selected using  
the same guidelines outlined for MOSFET  
Output Capacitor Selection  
voltage selection. For  
a
low duty cycle  
Select the output capacitor for voltage rating,  
capacitance and Equivalent Series Resistance  
(ESR). Nominally the voltage rating is selected  
to be twice as large as the output voltage.  
Select the capacitance to satisfy the  
specification for output voltage overshoot or  
undershoot caused by current step load. A  
steady-state output current IOUT corresponds to  
inductor stored energy of ½ L IOUT2. A sudden  
decrease in IOUT forces the energy surplus in L  
application such as the circuit shown on first  
page, the Schottky is conducting most of the  
time and its conduction losses are the largest  
component of losses in the converter.  
Conduction losses can be estimated from:  
Vout  
Vin  
Pc = Vf × Iout × 1−  
to be absorbed by COUT  
.
Jan28-08 RevG  
SP6125: TSOT-6 PFET Buck Controller  
2007 Exar Corporation  
7
General Overview  
This causes an overshoot in output voltage that  
is corrected by power switch reduced duty  
cycle. Use the following equation to calculate  
Input Capacitor Selection  
Select the input capacitor for Voltage,  
Capacitance, ripple current, ESR and ESL.  
Voltage rating is nominally selected to be twice  
the input voltage. The RMS value of input  
capacitor current, assuming a low inductor  
ripple current (Irip), can be calculated from:  
C
OUT:  
2
2
I2 I1  
Cout = L×  
2
2
Vos - Vout  
Icin = Iout × D  
(
1D  
)
Where:  
L is the output inductance  
I2 is the step load high current  
I1 is the step load low current  
In general total input voltage ripple should be  
kept below 1.5% of VIN (not to exceed 180mV).  
Input voltage ripple has three components:  
ESR and ESL cause a step voltage drop upon  
turn on of the MOSFET. During on time  
capacitor discharges linearly as it supplies IOUT  
- IIN. The contribution to Input voltage ripple by  
each term can be calculated from:  
Vos is output voltage including overshoot  
VOUT is steady state output voltage  
Output voltage undershoot calculation is more  
complicated. Test results for SP6125 buck  
circuits show that undershoot is approximately  
equal to overshoot. Therefore above equation  
provides a satisfactory method for calculating  
Iout ×Vout ×  
(
Vin Vout  
)
V,Cin =  
fs×Cin×Vin2  
C
OUT.  
Select ESR such that output voltage ripple  
(VRIP) specification is met. There are two  
components to VRIP: First component arises  
from charge transferred to and from COUT  
during each cycle. The second component of  
V,ESR = ESR  
V, ESL = ESL  
(
Iout 0.5Irip  
)
)
(
Iout 0.5Irip  
Trise  
VRIP is due to inductor ripple current flowing  
Where Trise is the rise time of current through  
capacitor  
through output capacitor’s ESR. It can be  
calculated from:  
Total input voltage ripple is sum of the above:  
2  
1
2
V,Tot = ∆V,Cin + ∆V, ESR + ∆V,ESL  
Vrip = Irip × ESR +  
8×Cout × fs  
In circuits where converter input voltage is  
applied via a mechanical switch excessive  
ringing may be present at turn-on that may  
interfere with smooth startup of SP6126.  
Addition of an inexpensive 100µF Aluminum  
Electrolytic capacitor at the input will help  
reduce ringing and restore a smooth startup.  
Where:  
I
RIP is inductor ripple current  
f
s is switching frequency  
C
OUT is output capacitor calculated above  
Note that a smaller inductor results in a higher  
RIP, therefore requiring a larger COUT and/or  
I
lower ESR in order to meet VRIP  
.
Jan28-08 RevG  
SP6125: TSOT-6 PFET Buck Controller  
2007 Exar Corporation  
8
VIN  
C1  
4.7uF  
C2  
4.7uF  
24V  
Q1  
2
FDS4685  
1
3
Gate  
LX  
GND  
VOUT  
Vin  
L1, IHLP-2525CZ  
8.2uH, 68mOhm, 4A  
Rs 2k  
6
C6  
0.1uF  
C4  
22uF  
C5  
3.3V  
0-3A  
SP6125  
Ds  
RZ  
22uF  
MBRA340T3G 2K  
R1  
300k, 1%  
VDR  
CZ  
4
47pF  
GND  
VFB  
GND  
5
R2  
66.5k, 1%  
D1 1N4148  
SHDN  
High=Off  
Figure 4- Application circuit for Vin=24V  
TYPICAL PERFORMANCE CHARACTERISTICS  
SP6125 Efficiency versus Iout, Vin=24V,Ta=25C  
90  
80  
70  
60  
50  
Vout=3.3V  
0.0  
0.5  
1.0  
1.5  
2.0  
2.5  
3.0  
Iout (A)  
Figure 5- Efficiency at VIN = 24 V , TA= 25˚C, natural convection  
Jan28-08 RevG  
SP6125: TSOT-6 PFET Buck Controller  
2007 Exar Corporation  
9
TYPICAL PERFORMANCE CHARACTERISTICS  
Figure 6- Step load 1.2-2.8A,  
ch1: VIN; ch2: VOUT; ch3: IOUT  
Figure 9- Output ripple at 0A is 12mV,  
ch1: VIN; ch2: VOUT; ch3: IOUT  
Figure 7- Startup no load,  
ch1: VIN; ch2: VOUT, ch3: IOUT  
Figure 10- Output ripple at 3A is 32mV,  
ch1: VIN; ch2: VOUT; ch3: IOUT  
Figure 8- Start up 3A,  
ch1: VIN; ch2: VOUT; ch3: IOUT  
Jan28-08 RevG  
SP6125: TSOT-6 PFET Buck Controller  
2007 Exar Corporation  
10  
PACKAGE: 6PIN TSOT  
Jan28-08 RevG  
SP6125: TSOT-6 PFET Buck Controller  
2007 Exar Corporation  
11  
ORDERING INFORMATION  
Package  
Part Number  
Temperature Range  
SP6125EK1-L………………………………….-40°C to +125°C…………..….…(Lead Free) 6 Pin TSOT  
SP6125EK1-L/TR…………………………....-40°C to +125°C………..……..….(Lead Free) 6 Pin TSOT  
/TR = Tape and Reel  
Pack Quantity for Tape and Reel is 2500  
For further assistance:  
Email:  
customersupport@exar.com  
EXAR Technical Documentation: http://www.exar.com/TechDoc/default.aspx?  
Exar Corporation  
Headquarters and  
Sales Office  
48720 Kato Road  
Fremont, CA 94538  
main: 510-668-7000  
fax: 510-668-7030  
EXAR Corporation reserves the right to make changes to the products contained in this publication  
in order to improve design, performance or reliability. EXAR Corporation assumes no responsibility  
for the use of any circuits described herein, conveys no license under any patent or other right, and  
makes no representation that the circuits are free of patent infringement. Charts and schedules  
contained here in are only for illustration purposes and may vary depending upon a user’s specific  
application. While the information in this publication has been carefully checked; no responsibility,  
however, is assumed for inaccuracies.  
EXAR Corporation does not recommend the use of any of its products in life support applications  
where the failure or malfunction of the product can reasonably be expected to cause failure of the life  
support system or to significantly affect its safety or effectiveness. Products are not authorized for  
use in such applications unless EXAR Corporation receives, in writing, assurances to its satisfaction  
that: (a) the risk of injury or damage has been minimized; (b) the user assumes all such risks; (c)  
potential liability of EXAR Corporation is adequately protected under the circumstances.  
Jan28-08 RevG  
SP6125: TSOT-6 PFET Buck Controller  
2007 Exar Corporation  
12  
配单直通车
SP6125EK1-L产品参数
型号:SP6125EK1-L
是否Rohs认证: 符合
生命周期:Transferred
包装说明:ROHS COMPLIANT, MO-193AA, TSOT-6
Reach Compliance Code:unknown
风险等级:5.74
模拟集成电路 - 其他类型:SWITCHING CONTROLLER
控制模式:VOLTAGE-MODE
控制技术:PULSE WIDTH MODULATION
最大输入电压:29 V
最小输入电压:4.5 V
标称输入电压:12 V
JESD-30 代码:R-PDSO-G6
JESD-609代码:e3
长度:2.9 mm
湿度敏感等级:1
功能数量:1
端子数量:6
最高工作温度:85 °C
最低工作温度:-40 °C
封装主体材料:PLASTIC/EPOXY
封装代码:TSSOP
封装形状:RECTANGULAR
封装形式:SMALL OUTLINE, THIN PROFILE, SHRINK PITCH
峰值回流温度(摄氏度):260
认证状态:Not Qualified
座面最大高度:1.1 mm
表面贴装:YES
切换器配置:SINGLE
最大切换频率:345 kHz
温度等级:INDUSTRIAL
端子面层:Matte Tin (Sn)
端子形式:GULL WING
端子节距:0.95 mm
端子位置:DUAL
处于峰值回流温度下的最长时间:NOT SPECIFIED
宽度:1.6 mm
Base Number Matches:1
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