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    产品型号TPA0212PWP的Datasheet PDF文件预览

    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    PWP PACKAGE  
    (TOP VIEW)  
    Compatible With PC 99 Desktop Line-Out  
    Into 10-kΩ Load  
    Internal Gain Control, Which Eliminates  
    External Gain-Setting Resistors  
    1
    24  
    23  
    22  
    21  
    20  
    19  
    18  
    17  
    16  
    15  
    14  
    13  
    GND  
    GAIN0  
    GAIN1  
    LOUT+  
    LLINEIN  
    LHPIN  
    GND  
    2
    RLINEIN  
    SHUTDOWN  
    ROUT+  
    RHPIN  
    3
    2-W/Ch Output Power Into 3-Ω Load  
    Input MUX Select Terminal  
    PC-Beep Input  
    4
    5
    6
    V
    DD  
    Depop Circuitry  
    7
    PV  
    PV  
    DD  
    DD  
    8
    RIN  
    LOUT–  
    LIN  
    BYPASS  
    GND  
    HP/LINE  
    ROUT–  
    SE/BTL  
    PC-BEEP  
    GND  
    Stereo Input MUX  
    9
    Fully Differential Input  
    10  
    11  
    12  
    Low Supply Current and Shutdown Current  
    Surface-Mount Power Packaging  
    24-Pin TSSOP PowerPAD  
    description  
    The TPA0212 is a stereo audio power amplifier in a 24-pin TSSOP thermally enhanced package capable of  
    delivering 2 W of continuous RMS power per channel into 3-Ω loads. This device minimizes the number of  
    external components needed, simplifying the design, and freeing up board space for other features. When  
    driving 1 W into 8-Ω speakers, the TPA0212 has less than 0.8% THD+N across its specified frequency range.  
    Included within this device is integrated depop circuitry that virtually eliminates transients that cause noise in  
    the speakers.  
    Amplifier gain is internally configured and controlled by way of two terminals (GAIN0 and GAIN1). BTL gain  
    settings of 2, 6, 12, and 24 V/V are provided, while SE gain is always configured as 1 V/V for headphone drive.  
    An internal input MUX allows two sets of stereo inputs to the amplifier. The HP/LINE terminal allows the user  
    to select which MUX input is active regardless of whether the amplifier is in SE or BTL mode. In notebook  
    applications, where internal speakers are driven as BTL and the line outputs (often headphone drive) are  
    required to be SE, the TPA0212 automatically switches into SE mode when the SE/BTL input is activated, and  
    this reduces the gain to 1 V/V.  
    The TPA0212 consumes only 6 mA of supply current during normal operation. A miserly shutdown mode  
    reduces the supply current to less than 150 µA.  
    The PowerPAD package (PWP) delivers a level of thermal performance that was previously achievable only  
    in TO-220-type packages. Thermal impedances of approximately 35°C/W are readily realized in multilayer PCB  
    applications. This allows the TPA0212 to operate at full power into 8-Ω loads at an ambient temperature of 85°C.  
    Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of  
    Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.  
    PowerPAD is a trademark of Texas Instruments Incorporated.  
    Copyright 1999, Texas Instruments Incorporated  
    PRODUCTION DATA information is current as of publication date.  
    Products conform to specifications per the terms of Texas Instruments  
    standard warranty. Production processing does not necessarily include  
    testing of all parameters.  
    1
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    functional block diagram  
    RHPIN  
    R
    MUX  
    RLINEIN  
    –
    +
    ROUT+  
    RIN  
    –
    +
    ROUT–  
    PC-  
    PC-BEEP  
    Beep  
    PV  
    DD  
    Power  
    Management  
    Depop  
    Circuitry  
    V
    DD  
    Gain/  
    MUX  
    GAIN0  
    GAIN1  
    SE/BTL  
    BYPASS  
    SHUTDOWN  
    Control  
    GND  
    HP/LINE  
    LHPIN  
    L
    MUX  
    LLINEIN  
    –
    +
    LOUT+  
    LIN  
    –
    +
    LOUT–  
    2
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    AVAILABLE OPTIONS  
    PACKAGED DEVICE  
    †
    T
    A
    TSSOP  
    (PWP)  
    –40°C to 85°C  
    TPA0212PWP  
    †
    The PWP package is available taped and  
    reeled. To order a taped and reeled part, add  
    the suffix  
    R to the part number (e.g.,  
    TPA0212PWPR).  
    Terminal Functions  
    TERMINAL  
    NAME  
    BYPASS  
    I/O  
    DESCRIPTION  
    NO.  
    11  
    2
    Tap to voltage divider for internal mid-supply bias generator  
    Bit 0 of gain control  
    GAIN0  
    GAIN1  
    I
    I
    3
    Bit 1 of gain control  
    1, 12,  
    13, 24  
    GND  
    Ground connection for circuitry. Connected to the thermal pad.  
    LHPIN  
    LIN  
    6
    10  
    5
    I
    I
    Left channel headphone input, selected when SE/BTL is held high  
    Common left input for fully differential input. AC ground for single-ended inputs.  
    Left channel line input, selected when SE/BTL is held low  
    LLINEIN  
    LOUT+  
    LOUT–  
    I
    4
    O
    O
    Left channel positive output in BTL mode and positive output in SE mode  
    Left channel negative output in BTL mode and high-impedance in SE mode  
    9
    The input for PC Beep mode. PC-BEEP is enabled when a > 1-V (peak-to-peak) square wave is input  
    to PC-BEEP or PCB ENABLE is high.  
    PC-BEEP  
    14  
    I
    HP/LINE is the input MUX control input. When the HP/LINE terminal is held high, the headphone inputs  
    (LHPIN or RHPIN [6, 20]) are active. When the HP/LINE terminal is held low, the line BTL inputs (LLINEIN  
    or RLINEIN [5, 23]) are active.  
    HP/LINE  
    17  
    I
    PV  
    DD  
    7, 18  
    20  
    8
    I
    I
    Power supply for output stage  
    RHPIN  
    Right channel headphone input, selected when SE/BTL is held high  
    Common right input for fully differential input. AC ground for single-ended inputs.  
    Right channel line input, selected when SE/BTL is held low  
    RIN  
    I
    RLINEIN  
    ROUT+  
    ROUT–  
    SHUTDOWN  
    SE/BTL  
    23  
    21  
    16  
    22  
    15  
    19  
    I
    O
    O
    I
    Right channel positive output in BTL mode and positive output in SE mode  
    Right channel negative output in BTL mode and high-impedance in SE mode  
    Places entire IC in shutdown mode when held low, except PC-BEEP remains active  
    Hold SE/BTL low for BTL mode and hold high for SE mode.  
    I
    V
    DD  
    I
    Analog V  
    DD  
    input supply. This terminal needs to be isolated from PV to achieve highest performance.  
    DD  
    3
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    †
    absolute maximum ratings over operating free-air temperature range (unless otherwise noted)  
    Supply voltage, V  
    . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 V  
    DD  
    Input voltage, V . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to V +0.3 V  
    I
    DD  
    Continuous total power dissipation . . . . . . . . . . . . . . . . . . . . . internally limited (see Dissipation Rating Table)  
    Operating free-air temperature range, T . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to 85°C  
    Operating junction temperature range, T . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to 150°C  
    A
    J
    Storage temperature range, T  
    . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –65°C to 150°C  
    stg  
    Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 260°C  
    †
    Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and  
    functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not  
    implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.  
    DISSIPATION RATING TABLE  
    PACKAGE  
    T
    A
    ≤ 25°C  
    DERATING FACTOR  
    T
    A
    = 70°C  
    T = 85°C  
    A
    ‡
    PWP  
    2.7 W  
    21.8 mW/°C  
    1.7 W  
    1.4 W  
    ‡
    Please see the Texas Instruments document, PowerPAD Thermally Enhanced Package Application Report  
    (literature number SLMA002), for more information on the PowerPAD package. The thermal data was  
    measured on a PCB layout based on the information in the section entitled Texas InstrumentsRecommended  
    Board for PowerPAD on page 33 of the before mentioned document.  
    recommended operating conditions  
    MIN  
    4.5  
    4
    MAX  
    UNIT  
    Supply voltage, V  
    DD  
    5.5  
    V
    SE/BTL, HP/LINE  
    SHUTDOWN  
    High-level input voltage, V  
    V
    IH  
    2
    SE/BTL, HP/LINE  
    SHUTDOWN  
    3
    0.8  
    85  
    Low-level input voltage, V  
    V
    IL  
    Operating free-air temperature, T  
    –40  
    °C  
    A
    electrical characteristics at specified free-air temperature, V  
    noted)  
    = 5 V, T = 25°C (unless otherwise  
    A
    DD  
    PARAMETER  
    Output offset voltage (measured differentially)  
    Power supply rejection ratio  
    TEST CONDITIONS  
    MIN  
    TYP  
    MAX  
    UNIT  
    mV  
    |V  
    |
    V = 0, A = –2 V/V  
    25  
    OO  
    PSRR  
    I
    v
    V
    DD  
    = 4 V to 5 V  
    77  
    dB  
    V
    = 5.5 V,  
    DD  
    |I  
    |I  
    |
    High-level input current  
    Low-level input current  
    900  
    900  
    nA  
    nA  
    IH  
    V = V  
    I
    DD  
    V
    = 5.5 V,  
    DD  
    |
    IL  
    V = 0 V  
    I
    BTL mode  
    SE mode  
    6
    3
    8
    4
    I
    I
    Supply current  
    mA  
    DD  
    Supply current, shutdown mode  
    150  
    300  
    µA  
    DD(SD)  
    4
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    operating characteristics, V  
    = 5 V, T = 25°C, R = 8 Ω, Gain = –2 V/V, BTL mode  
    DD  
    A
    L
    PARAMETER  
    TEST CONDITIONS  
    MIN  
    TYP  
    MAX  
    UNIT  
    THD = 1%,  
    f = 1 kHz,  
    P
    O
    Output power  
    1.9  
    W
    R
    = 4 Ω  
    L
    THD + N Total harmonic distortion plus noise  
    P
    = 1 W,  
    f = 20 Hz to 15 kHz  
    0.75%  
    >15  
    O
    B
    Maximum output power bandwidth  
    Supply ripple rejection ratio  
    Signal-to-noise ratio  
    THD = 5%  
    kHz  
    dB  
    OM  
    f = 1 kHz,  
    BTL mode  
    68  
    C
    C
    = 0.47 µF  
    = 0.47 µF,  
    B
    B
    SNR  
    105  
    16  
    dB  
    BTL mode  
    SE mode  
    V
    Noise output voltage  
    Input impedance  
    µV  
    RMS  
    n
    f = 20 Hz to 20 kHz  
    30  
    Z
    I
    See Table 1  
    TYPICAL CHARACTERISTICS  
    Table of Graphs  
    FIGURE  
    1, 4–7, 10–13,  
    16–19, 21  
    vs Output power  
    vs Frequency  
    THD+N  
    Total harmonic distortion plus noise  
    2, 3, 8, 9, 14,  
    15, 20, 22  
    vs Output voltage  
    vs Bandwidth  
    vs Frequency  
    vs Frequency  
    vs Frequency  
    vs Frequency  
    23  
    24  
    V
    Output noise voltage  
    Supply ripple rejection ratio  
    Crosstalk  
    n
    25, 26  
    27–29  
    30  
    Shutdown attenuation  
    Signal-to-noise ratio  
    Closed loop respone  
    Output power  
    SNR  
    31  
    32–35  
    36, 37  
    38, 39  
    40  
    P
    P
    vs Load resistance  
    vs Output power  
    O
    Power dissipation  
    D
    vs Ambient temperature  
    5
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    TYPICAL CHARACTERISTICS  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    vs  
    vs  
    OUTPUT POWER  
    FREQUENCY  
    10%  
    10%  
    1%  
    A
    = –2 V/V  
    P
    R
    BTL  
    = 1.75 W  
    = 3 Ω  
    V
    O
    L
    f = 1 kHz  
    BTL  
    R
    = 4 Ω  
    A
    V
    = –24 V/V  
    L
    1%  
    R
    = 8 Ω  
    L
    R
    = 3 Ω  
    L
    A
    V
    = –12 V/V  
    A = –2 V/V  
    V
    0.1%  
    0.1%  
    0.01%  
    A
    V
    = –6 V/V  
    0.01%  
    0.5 0.75  
    1
    1.25 1.5 1.75  
    2
    2.25 2.5 2.75  
    3
    20  
    100  
    1k  
    10k 20k  
    P
    O
    – Output Power – W  
    f – Frequency – Hz  
    Figure 1  
    Figure 2  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    vs  
    vs  
    FREQUENCY  
    OUTPUT POWER  
    10%  
    10%  
    R
    = 3 Ω  
    = –2 V/V  
    L
    A
    V
    BTL  
    f = 15 kHz  
    1%  
    1%  
    P
    O
    = 1.0 W  
    f = 1 kHz  
    P
    O
    = 0.5 W  
    0.1%  
    0.01%  
    0.1%  
    f = 20 Hz  
    R
    = 3 Ω  
    = –2 V/V  
    L
    A
    V
    P
    = 1.75 W  
    O
    BTL  
    0.01%  
    20  
    100  
    1k  
    10k 20k  
    0.01  
    0.1  
    1
    10  
    f – Frequency – Hz  
    P
    O
    – Output Power – W  
    Figure 3  
    Figure 4  
    6
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    TYPICAL CHARACTERISTICS  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    vs  
    vs  
    OUTPUT POWER  
    OUTPUT POWER  
    10%  
    10%  
    f = 15 kHz  
    f = 1 kHz  
    f = 15 kHz  
    1%  
    1%  
    f = 1 kHz  
    f = 20 Hz  
    f = 20 Hz  
    0.1%  
    0.1%  
    R
    = 3 Ω  
    = –6 V/V  
    L
    R
    = 3 Ω  
    = –12 V/V  
    L
    A
    V
    A
    V
    BTL  
    BTL  
    0.01%  
    0.01%  
    0.01  
    0.1  
    1
    10  
    0.01  
    0.1  
    1
    10  
    P
    O
    – Output Power – W  
    P
    O
    – Output Power – W  
    Figure 5  
    Figure 6  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    vs  
    vs  
    OUTPUT POWER  
    FREQUENCY  
    10%  
    10%  
    f = 15 kHz  
    P
    R
    BTL  
    = 1.75 W  
    = 3 Ω  
    O
    L
    A
    V
    = –24 V/V  
    f = 1 kHz  
    f = 20 Hz  
    1%  
    1%  
    A
    V
    = –12 V/V  
    A
    V
    = –2 V/V  
    0.1%  
    0.01%  
    0.1%  
    R
    = 3 Ω  
    = –24 V/V  
    L
    A
    V
    = –6 V/V  
    1k  
    A
    V
    BTL  
    0.01%  
    0.01  
    0.1  
    1
    10  
    20  
    100  
    10k 20k  
    P
    O
    – Output Power – W  
    f – Frequency – Hz  
    Figure 7  
    Figure 8  
    7
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    TYPICAL CHARACTERISTICS  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    vs  
    vs  
    FREQUENCY  
    OUTPUT POWER  
    10%  
    10%  
    1%  
    R
    = 4 Ω  
    = –2 V/V  
    L
    R
    = 4 Ω  
    = –2 V/V  
    L
    A
    V
    A
    V
    BTL  
    BTL  
    f = 15 kHz  
    f = 1 kHz  
    1%  
    P
    O
    = 1.5 W  
    P
    O
    = 0.25 W  
    0.1%  
    0.01%  
    0.1%  
    P
    O
    = 1.0 W  
    f = 20 Hz  
    0.01%  
    20  
    100  
    1k  
    10k 20k  
    0.01  
    0.1  
    1
    10  
    f – Frequency – Hz  
    P
    O
    – Output Power – W  
    Figure 9  
    Figure 10  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    vs  
    vs  
    OUTPUT POWER  
    OUTPUT POWER  
    10%  
    10%  
    f = 15 kHz  
    f = 15 kHz  
    1%  
    1%  
    f = 1 kHz  
    f = 20 Hz  
    f = 1 kHz  
    f = 20 Hz  
    0.1%  
    0.1%  
    R
    = 4 Ω  
    = –6 V/V  
    L
    R
    = 4 Ω  
    = –12 V/V  
    L
    A
    V
    A
    V
    BTL  
    BTL  
    0.01%  
    0.01%  
    0.01  
    0.1  
    1
    10  
    0.01  
    0.1  
    1
    10  
    P
    O
    – Output Power – W  
    P
    O
    – Output Power – W  
    Figure 11  
    Figure 12  
    8
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    TYPICAL CHARACTERISTICS  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    vs  
    vs  
    OUTPUT POWER  
    FREQUENCY  
    10%  
    1%  
    10%  
    R
    = 8 Ω  
    = –2 V/V  
    L
    f = 15 kHz  
    A
    V
    BTL  
    f = 1 kHz  
    f = 20 Hz  
    1%  
    0.1%  
    0.01%  
    0.1%  
    P
    O
    = 0.25 W  
    P
    = 1.0 W  
    O
    R
    = 4 Ω  
    = –24 V/V  
    L
    A
    V
    BTL  
    P
    O
    = 0.5 W  
    1k  
    0.01%  
    0.01  
    0.1  
    1
    10  
    20  
    100  
    10k 20k  
    P
    O
    – Output Power – W  
    f – Frequency – Hz  
    Figure 13  
    Figure 14  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    vs  
    vs  
    FREQUENCY  
    OUTPUT POWER  
    10%  
    10%  
    P
    R
    BTL  
    = 1 W  
    = 8 Ω  
    O
    L
    R
    = 8 Ω  
    = –2 V/V  
    L
    A
    V
    BTL  
    A
    V
    = –24 V/V  
    1%  
    f = 15 kHz  
    f = 1 kHz  
    1%  
    A
    V
    = –12 V/V  
    A
    V
    = –2 V/V  
    0.1%  
    0.01%  
    0.1%  
    A
    = –6 V/V  
    V
    f = 20 Hz  
    0.01%  
    20  
    100  
    1k  
    f – Frequency – Hz  
    10k 20k  
    0.01  
    0.1  
    1
    10  
    P
    O
    – Output Power – W  
    Figure 15  
    Figure 16  
    9
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    TYPICAL CHARACTERISTICS  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    vs  
    vs  
    OUTPUT POWER  
    OUTPUT POWER  
    10%  
    10%  
    R
    = 8 Ω  
    = –6 V/V  
    L
    A
    V
    BTL  
    f = 15 kHz  
    f = 15 kHz  
    1%  
    1%  
    f = 1 kHz  
    f = 20 Hz  
    f = 1 kHz  
    f = 20 Hz  
    0.1%  
    0.1%  
    R
    = 8 Ω  
    = –12 V/V  
    L
    A
    V
    BTL  
    0.01%  
    0.01%  
    0.01  
    0.1  
    1
    10  
    0.01  
    0.1  
    P – Output Power – W  
    O
    1
    10  
    P
    O
    – Output Power – W  
    Figure 17  
    Figure 18  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    vs  
    vs  
    OUTPUT POWER  
    FREQUENCY  
    10%  
    10%  
    R
    A
    SE  
    = 32 Ω  
    = –1 V/V  
    L
    V
    f = 15 kHz  
    1%  
    1%  
    f = 1 kHz  
    f = 20 Hz  
    P
    O
    = 25 mW  
    0.1%  
    0.1%  
    P
    O
    = 50 mW  
    R
    A
    BTL  
    = 8 Ω  
    = –24 V/V  
    L
    V
    P
    O
    = 75 mW  
    0.01%  
    0.01%  
    0.01  
    0.1  
    1
    10  
    20  
    100  
    1k  
    10k 20k  
    P
    O
    – Output Power – W  
    f – Frequency – Hz  
    Figure 19  
    Figure 20  
    10  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    TYPICAL CHARACTERISTICS  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    vs  
    vs  
    OUTPUT POWER  
    FREQUENCY  
    10%  
    1%  
    10%  
    R
    A
    SE  
    = 32 Ω  
    = –1 V/V  
    R
    A
    SE  
    = 10 kΩ  
    = –1 V/V  
    L
    V
    L
    V
    1%  
    f = 15 kHz  
    0.1%  
    0.1%  
    f = 1 kHz  
    f = 20 Hz  
    V = 1 V  
    O RMS  
    0.01%  
    0.001%  
    0.01%  
    0.01  
    0.1  
    1
    20  
    100  
    1k  
    10k 20k  
    P
    O
    – Output Power – W  
    f – Frequency – Hz  
    Figure 21  
    Figure 22  
    TOTAL HARMONIC DISTORTION PLUS NOISE  
    OUTPUT NOISE VOLTAGE  
    vs  
    vs  
    OUTPUT VOLTAGE  
    BANDWIDTH  
    10%  
    1%  
    100  
    90  
    R
    A
    SE  
    = 10 kΩ  
    = –1 V/V  
    V
    R
    = 5 V  
    L
    V
    DD  
    = 4Ω  
    L
    80  
    70  
    60  
    50  
    40  
    30  
    20  
    A
    = –24 V/V  
    V
    0.1%  
    f = 20 Hz  
    f = 15 kHz  
    A
    = –12 V/V  
    V
    0.01%  
    A
    V
    = –6 V/V  
    f = 1 kHz  
    10  
    0
    A
    V
    = –2 V/V  
    0.001%  
    0.1  
    1
    3
    10  
    100  
    1k  
    10k  
    V
    O
    – Output Voltage – V  
    RMS  
    BW – Bandwidth – Hz  
    Figure 23  
    Figure 24  
    11  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    TYPICAL CHARACTERISTICS  
    SUPPLY RIPPLE REJECTION RATIO  
    SUPPLY RIPPLE REJECTION RATIO  
    vs  
    vs  
    FREQUENCY  
    FREQUENCY  
    0
    –20  
    –40  
    –60  
    –80  
    0
    –20  
    –40  
    –60  
    –80  
    R
    C
    BTL  
    = 8 Ω  
    = 0.47 µF  
    L
    B
    R
    C
    SE  
    = 32 Ω  
    = 0.47 µF  
    L
    B
    A
    = –24 V/V  
    = –2 V/V  
    V
    A
    V
    = –1 V/V  
    A
    V
    –100  
    –120  
    –100  
    –120  
    20  
    100  
    1k  
    10k 20k  
    20  
    100  
    1k  
    10k 20k  
    f – Frequency – Hz  
    f – Frequency – Hz  
    Figure 25  
    Figure 26  
    CROSSTALK  
    vs  
    FREQUENCY  
    CROSSTALK  
    vs  
    FREQUENCY  
    0
    –20  
    –40  
    –60  
    –80  
    0
    –20  
    –40  
    –60  
    –80  
    P
    R
    A
    BTL  
    = 1 W  
    = 8 Ω  
    = –2 V/V  
    O
    L
    v
    P
    R
    A
    = 1 W  
    = 8 Ω  
    =– 24 V/V  
    O
    L
    v
    BTL  
    LEFT TO RIGHT  
    RIGHT TO LEFT  
    LEFT TO RIGHT  
    RIGHT TO LEFT  
    –100  
    –120  
    –100  
    –120  
    20  
    100  
    1k  
    10k 20k  
    20  
    100  
    1k  
    10k 20k  
    f – Frequency – Hz  
    f – Frequency – Hz  
    Figure 27  
    Figure 28  
    12  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    TYPICAL CHARACTERISTICS  
    CROSSTALK  
    SHUTDOWN ATTENUATION  
    vs  
    vs  
    FREQUENCY  
    FREQUENCY  
    0
    –20  
    –40  
    –60  
    –80  
    0
    –20  
    –40  
    –60  
    –80  
    V
    R
    A
    SE  
    = 1 V  
    RMS  
    O
    L
    v
    V = 1 V  
    I RMS  
    = 10 kΩ  
    = –1 V/V  
    R
    = 10 kΩ, SE  
    L
    R
    = 32 Ω, SE  
    L
    LEFT TO RIGHT  
    –100  
    –120  
    –100  
    –120  
    R
    = 8 Ω, BTL  
    L
    RIGHT TO LEFT  
    20  
    100  
    1k  
    10k 20k  
    20  
    100  
    1k  
    10k 20k  
    f – Frequency – Hz  
    f – Frequency – Hz  
    Figure 29  
    Figure 30  
    SIGNAL-TO-NOISE RATIO  
    vs  
    FREQUENCY  
    140  
    130  
    P
    R
    BTL  
    = 1 W  
    = 8 Ω  
    O
    L
    120  
    110  
    A = –6 V/V  
    V
    A
    V
    = –2 V/V  
    A
    V
    = – 24 V/V  
    100  
    90  
    A
    V
    = –12 V/V  
    80  
    70  
    60  
    20  
    100  
    1k  
    10k 20k  
    f – Frequency – Hz  
    Figure 31  
    13  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    TYPICAL CHARACTERISTICS  
    CLOSED LOOP RESPONSE  
    180°  
    10  
    7.5  
    Gain  
    90°  
    5
    2.5  
    Phase  
    0°  
    0
    –2.5  
    –5  
    R
    = 8 Ω  
    = –2 V/V  
    L
    –90°  
    –180°  
    A
    V
    BTL  
    –7.5  
    –10  
    10  
    100  
    1k  
    10k  
    100k  
    1M  
    f – Frequency – Hz  
    Figure 32  
    CLOSED LOOP RESPONSE  
    180°  
    90°  
    30  
    25  
    20  
    15  
    Gain  
    Phase  
    0°  
    10  
    5
    R
    = 8 Ω  
    = –6 V/V  
    L
    0
    –90°  
    –180°  
    A
    V
    BTL  
    –5  
    –10  
    10  
    100  
    1k  
    10k  
    100k  
    1M  
    f – Frequency – Hz  
    Figure 33  
    14  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    TYPICAL CHARACTERISTICS  
    CLOSED LOOP RESPONSE  
    180°  
    30  
    25  
    Gain  
    90°  
    20  
    15  
    Phase  
    0°  
    10  
    5
    R
    = 8 Ω  
    = –12 V/V  
    L
    0
    –90°  
    A
    V
    BTL  
    –5  
    –10  
    –180°  
    10  
    100  
    1k  
    10k  
    100k  
    1M  
    f – Frequency – Hz  
    Figure 34  
    CLOSED LOOP RESPONSE  
    Gain  
    180°  
    90°  
    30  
    25  
    20  
    15  
    Phase  
    0°  
    10  
    5
    R
    = 8 Ω  
    = –24 V/V  
    L
    0
    –90°  
    –180°  
    A
    V
    BTL  
    –5  
    –10  
    10  
    100  
    1k  
    10k  
    100k  
    1M  
    f – Frequency – Hz  
    Figure 35  
    15  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    TYPICAL CHARACTERISTICS  
    OUTPUT POWER  
    vs  
    LOAD RESISTANCE  
    OUTPUT POWER  
    vs  
    LOAD RESISTANCE  
    3.5  
    3
    1500  
    1250  
    1000  
    750  
    A
    BTL  
    = –2 V/V  
    V
    A = –1 V/V  
    V
    SE  
    2.5  
    2
    10% THD+N  
    1.5  
    1
    10% THD+N  
    500  
    1% THD+N  
    250  
    0
    0.5  
    0
    1% THD+N  
    16  
    0
    8
    16  
    24  
    32  
    40  
    48  
    56  
    64  
    0
    8
    24  
    32  
    40  
    48  
    56  
    64  
    R
    – Load Resistance – Ω  
    L
    R
    – Load Resistance – Ω  
    L
    Figure 36  
    Figure 37  
    POWER DISSIPATION  
    vs  
    OUTPUT POWER  
    POWER DISSIPATION  
    vs  
    OUTPUT POWER  
    1.8  
    1.6  
    0.4  
    3 Ω  
    0.35  
    0.3  
    1.4  
    1.2  
    1
    4 Ω  
    4 Ω  
    0.25  
    0.2  
    0.8  
    0.6  
    0.15  
    0.1  
    8 Ω  
    8 Ω  
    0.4  
    f = 1 kHz  
    BTL  
    Each Channel  
    f = 1 kHz  
    SE  
    Each Channel  
    32 Ω  
    0.05  
    0
    0.2  
    0
    0
    0.5  
    1
    1.5  
    2
    2.5  
    0
    0.1  
    0.2  
    0.3  
    0.4  
    0.5  
    0.6 0.7 0.8  
    P
    O
    – Output Power – W  
    P
    O
    – Output Power – W  
    Figure 38  
    Figure 39  
    16  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    TYPICAL CHARACTERISTICS  
    POWER DISSIPATION  
    vs  
    AMBIENT TEMPERATURE  
    7
    6
    Θ
    Θ
    Θ
    Θ
    = 45.9°C/W  
    = 45.2°C/W  
    = 31.2°C/W  
    = 18.6°C/W  
    JA1  
    JA2  
    JA3  
    JA4  
    Θ
    JA4  
    5
    4
    Θ
    Θ
    JA3  
    3
    2
    JA1,2  
    1
    0
    –40 –20  
    0
    20 40 60 80 100 120 140 160  
    T
    A
    – Ambient Temperature – °C  
    Figure 40  
    17  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    THERMAL INFORMATION  
    The thermally enhanced PWP package is based on the 24-pin TSSOP, but includes a thermal pad (see Figure 41)  
    to provide an effective thermal contact between the IC and the PWB.  
    Traditionally, surface mount and power have been mutually exclusive terms. A variety of scaled-down TO-220-type  
    packages have leads formed as gull wings to make them applicable for surface-mount applications. These packages,  
    however, have only two shortcomings: they do not address the very low profile requirements (<2 mm) of many of  
    today’s advanced systems, and they do not offer a terminal-count high enough to accommodate increasing  
    integration. Ontheotherhand, traditionallow-powersurface-mountpackagesrequirepower-dissipationderatingthat  
    severely limits the usable range of many high-performance analog circuits.  
    The PowerPAD package (thermally enhanced TSSOP) combines fine-pitch surface-mount technology with thermal  
    performance comparable to much larger power packages.  
    The PowerPAD package is designed to optimize the heat transfer to the PWB. Because of the very small size and  
    limited mass of a TSSOP package, thermal enhancement is achieved by improving the thermal conduction paths that  
    remove heat from the component. The thermal pad is formed using a patented lead-frame design and manufacturing  
    technique to provide a direct connection to the heat-generating IC. When this pad is soldered or otherwise thermally  
    coupled to an external heat dissipator, high power dissipation in the ultra-thin, fine-pitch, surface-mount package can  
    be reliably achieved.  
    DIE  
    Side View (a)  
    Thermal  
    Pad  
    DIE  
    End View (b)  
    Bottom View (c)  
    Figure 41. Views of Thermally Enhanced PWP Package  
    APPLICATION INFORMATION  
    selection of components  
    Figure 42 and Figure 43 are schematic diagrams of typical notebook computer application circuits.  
    18  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    Right  
    C
    IRHP  
    Head– 0.47 µF  
    phone  
    Input  
    Signal  
    RHPIN  
    20  
    R
    MUX  
    23 RLINEIN  
    C
    IRLINE  
    0.47 µF  
    Right  
    Line  
    –
    ROUT+ 21  
    +
    Input  
    Signal  
    8
    RIN  
    C
    RIN  
    0.47 µF  
    C
    OUTR  
    PC BEEP  
    Input  
    Signal  
    330 µF  
    14  
    PC–BEEP  
    –
    ROUT– 16  
    PC–  
    Beep  
    V
    DD  
    C
    PCB  
    0.47 µF  
    1 kΩ  
    +
    100 kΩ  
    See Note A  
    GAIN0  
    GAIN1  
    SE/BTL  
    2
    3
    PVDD 18  
    VDD 19  
    V
    Gain/  
    MUX  
    Control  
    DD  
    C
    SR  
    Depop  
    Circuitry  
    0.1 µF  
    15  
    V
    DD  
    C
    Power  
    ILHP  
    Left  
    0.47 µF  
    Management  
    C
    0.1 µF  
    BYPASS 11  
    SHUT–  
    HP/LINE  
    SR  
    17  
    Head–  
    phone  
    Input  
    DOWN  
    22  
    C
    BYP  
    0.47 µF  
    Signal  
    LHPIN  
    6
    5
    GND  
    To  
    L
    MUX  
    System  
    Control  
    1 kΩ  
    LLINEIN  
    C
    ILLINE  
    1,12,  
    13,24  
    0.47 µF  
    Left  
    Line  
    –
    +
    LOUT+  
    4
    C
    OUTL  
    330 µF  
    Input  
    Signal  
    10  
    LIN  
    C
    LIN  
    0.47 µF  
    –
    +
    LOUT–  
    9
    100 kΩ  
    NOTE A: A 0.1 µF ceramic capacitor should be placed as close as possible to the IC. For filtering lower–frequency noise signals, a larger  
    electrolytic capacitor of 10 µF or greater should be placed near the audio power amplifier.  
    Figure 42. Typical TPA0212 Application Circuit Using Single-Ended Inputs and Input MUX  
    19  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    APPLICATION INFORMATION  
    N/C  
    RHPIN  
    20  
    C
    IRIN–  
    0.47 µF  
    R
    MUX  
    Right  
    Negative  
    Differential  
    Input  
    23 RLINEIN  
    –
    ROUT+ 21  
    Signal  
    +
    C
    IRIN+  
    0.47 µF  
    Right  
    Positive  
    8
    RIN  
    Differential  
    Input  
    Signal  
    C
    OUTR  
    330 µF  
    PC BEEP  
    Input  
    Signal  
    14  
    PC–BEEP  
    –
    ROUT– 16  
    PC–  
    Beep  
    V
    DD  
    1 kΩ  
    +
    C
    PCB  
    0.47 µF  
    100 kΩ  
    See Note A  
    GAIN0  
    GAIN1  
    SE/BTL  
    2
    3
    PVDD 18  
    VDD 19  
    V
    Gain/  
    MUX  
    Control  
    DD  
    C
    SR  
    Depop  
    Circuitry  
    0.1 µF  
    15  
    V
    DD  
    Power  
    Management  
    C
    0.1 µF  
    BYPASS 11  
    SHUT–  
    HP/LINE  
    SR  
    17  
    N/C  
    DOWN  
    22  
    C
    BYP  
    0.47 µF  
    LHPIN  
    6
    5
    GND  
    To  
    System  
    Control  
    L
    MUX  
    1 kΩ  
    LLINEIN  
    C
    ILIN–  
    Left  
    Negative  
    Differential  
    Input  
    1,12,  
    13,24  
    0.47 µF  
    –
    +
    LOUT+  
    4
    C
    OUTL  
    330 µF  
    Signal  
    C
    ILIN+  
    0.47 µF  
    Left  
    Positive  
    10  
    LIN  
    Differential  
    Input  
    Signal  
    –
    +
    LOUT–  
    9
    100 kΩ  
    NOTE A: A 0.1 µF ceramic capacitor should be placed as close as possible to the IC. For filtering lower–frequency noise signals, a larger  
    electrolytic capacitor of 10 µF or greater should be placed near the audio power amplifier.  
    Figure 43. Typical TPA0212 Application Circuit Using Differential Inputs  
    20  
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    TPA0212  
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    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    APPLICATION INFORMATION  
    gain setting via GAIN0 and GAIN1 inputs  
    The gain of the TPA0212 is set by two input terminals, GAIN0 and GAIN1.  
    Table 1. Gain Settings  
    GAIN0  
    GAIN1  
    SE/BTL  
    A
    V
    0
    0
    1
    1
    X
    0
    1
    0
    1
    X
    0
    0
    0
    0
    1
    –2 V/V  
    –6 V/V  
    –12 V/V  
    –24 V/V  
    –1 V/V  
    The gains listed in Table 1 are realized by changing the taps on the input resistors inside the amplifier. This  
    causes the input impedance, Z , to be dependant on the gain setting. The actual gain settings are controlled  
    I
    by ratios of resistors, so the actual gain distribution from part-to-part is quite good. However, the input  
    impedance will shift by 30% due to shifts in the actual resistance of the input impedance.  
    For design purposes, the input network (discussed in the next section) should be designed assuming an input  
    impedance of 10 kΩ, which is the absolute minimum input impedance of the TPA0212. At the higher gain  
    settings, the input impedance could increase as high as 115 kΩ.  
    input resistance  
    Each gain setting is achieved by varying the input resistance of the amplifier, which can range from its smallest  
    value to over 6 times that value. As a result, if a single capacitor is used in the input high pass filter, the –3 dB  
    or cut-off frequency will also change by over 6 times. If an additional resistor is connected from the input pin  
    of the amplifier to ground, as shown in the figure below, the variation of the cut-off frequency will be much  
    reduced.  
    Z
    F
    C
    Z
    I
    IN  
    Input  
    Signal  
    R
    The typical input impedance at each gain setting is given in the table below:  
    A
    Z
    I
    v
    –24 V/V  
    –12 V/V  
    –6 V/V  
    –2 V/V  
    14 kΩ  
    26 kΩ  
    45.5 kΩ  
    91 kΩ  
    21  
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    SLOS284 – NOVEMBER 1999  
    APPLICATION INFORMATION  
    The –3 dB frequency can be calculated using equation 1:  
    1
    ƒ
    –3 dB  
    (1)  
    2
    C R R  
    I
    If the filter must be more accurate, the value of the capacitor should be increased while the value of the resistor  
    to ground should be decreased. In addition, the order of the filter could be increased.  
    input capacitor, C  
    I
    In the typical application an input capacitor, C , is required to allow the amplifier to bias the input signal to the  
    I
    proper dc level for optimum operation. In this case, C and the input impedance of the amplifier, Z , form a  
    I
    I
    high-pass filter with the corner frequency determined in equation 2.  
    –3 dB  
    (2)  
    1
    f
    c(highpass)  
    2 Z C  
    I
    I
    f
    c
    The value of C is important to consider as it directly affects the bass (low frequency) performance of the circuit.  
    I
    Consider the example where Z is 710 kΩ and the specification calls for a flat bass response down to 40 Hz.  
    I
    Equation 2 is reconfigured as equation 3.  
    1
    C
    I
    2 Z f  
    (3)  
    c
    I
    In this example, C is 5.6 nF so one would likely choose a value in the range of 5.6 nF to 1 µF. A further  
    I
    consideration for this capacitor is the leakage path from the input source through the input network (C ) and the  
    I
    feedback network to the load. This leakage current creates a dc offset voltage at the input to the amplifier that  
    reduces useful headroom, especially in high gain applications. For this reason a low-leakage tantalum or  
    ceramic capacitor is the best choice. When polarized capacitors are used, the positive side of the capacitor  
    should face the amplifier input in most applications as the dc level there is held at V /2, which is likely higher  
    DD  
    than the source dc level. Note that it is important to confirm the capacitor polarity in the application.  
    22  
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    SLOS284 – NOVEMBER 1999  
    APPLICATION INFORMATION  
    power supply decoupling, C  
    S
    The TPA0212 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling  
    to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also  
    prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is  
    achieved by using two capacitors of different types that target different types of noise on the power supply leads.  
    For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance  
    (ESR) ceramic capacitor, typically 0.1 µF placed as close as possible to the device V  
    filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 µF or greater placed near  
    lead, works best. For  
    DD  
    the audio power amplifier is recommended.  
    midrail bypass capacitor, C  
    BYP  
    The midrail bypass capacitor, C  
    start-uporrecoveryfromshutdownmode, C  
    , is the most critical capacitor and serves several important functions. During  
    BYP  
    determinestherateatwhichtheamplifierstartsup. Thesecond  
    BYP  
    function is to reduce noise produced by the power supply caused by coupling into the output drive signal. This  
    noise is from the midrail generation circuit internal to the amplifier, which appears as degraded PSRR and  
    THD+N.  
    Bypass capacitor, C  
    for the best THD and noise performance.  
    , values of 0.47 µF to 1 µF ceramic or tantalum low-ESR capacitors are recommended  
    BYP  
    output coupling capacitor, C  
    C
    In the typical single-supply SE configuration, an output coupling capacitor (C ) is required to block the dc bias  
    C
    at the output of the amplifier thus preventing dc currents in the load. As with the input coupling capacitor, the  
    output coupling capacitor and impedance of the load form a high-pass filter governed by equation 4.  
    –3 dB  
    1
    fc(high)  
    (4)  
    2 R C  
    L
    C
    f
    c
    Themaindisadvantage, fromaperformancestandpoint, istheloadimpedancesaretypicallysmall, whichdrives  
    the low-frequency corner higher, degrading the bass response. Large values of C are required to pass low  
    C
    frequencies into the load. Consider the example where a C of 330 µF is chosen and loads vary from 3 Ω,  
    C
    4 Ω, 8 Ω, 32 Ω, 10 kΩ, to 47 kΩ. Table 2 summarizes the frequency response characteristics of each  
    configuration.  
    23  
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    APPLICATION INFORMATION  
    Table 2. Common Load Impedances Vs Low Frequency Output Characteristics in SE Mode  
    R
    C
    Lowest Frequency  
    161 Hz  
    L
    C
    3 Ω  
    330 µF  
    330 µF  
    330 µF  
    330 µF  
    330 µF  
    330 µF  
    4 Ω  
    8 Ω  
    120 Hz  
    60 Hz  
    32 Ω  
    10,000 Ω  
    47,000 Ω  
    15 Hz  
    0.05 Hz  
    0.01 Hz  
    As Table 2 indicates, most of the bass response is attenuated into a 4-Ω load, an 8-Ω load is adequate,  
    headphone response is good, and drive into line level inputs (a home stereo for example) is exceptional.  
    using low-ESR capacitors  
    Low-ESR capacitors are recommended throughout this applications section. A real (as opposed to ideal)  
    capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this  
    resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this  
    resistance the more the real capacitor behaves like an ideal capacitor.  
    bridged-tied load versus single-ended mode  
    Figure 44 shows a Class-AB audio power amplifier (APA) in a BTL configuration. The TPA0212 BTL amplifier  
    consists of two Class-AB amplifiers driving both ends of the load. There are several potential benefits to this  
    differential drive configuration, but initially consider power to the load. The differential drive to the speaker  
    means that as one side is slewing up, the other side is slewing down, and vice versa. This in effect doubles the  
    voltage swing on the load as compared to a ground referenced load. Plugging 2 × V  
    equation, where voltage is squared, yields 4× the output power from the same supply rail and load impedance  
    into the power  
    O(PP)  
    (see equation 5).  
    V
    O(PP)  
    (5)  
    V
    (rms)  
    2 2  
    2
    V
    (rms)  
    Power  
    R
    L
    24  
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    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    APPLICATION INFORMATION  
    V
    DD  
    V
    O(PP)  
    2x V  
    R
    O(PP)  
    L
    V
    DD  
    –V  
    O(PP)  
    Figure 44. Bridge-Tied Load Configuration  
    In a typical computer sound channel operating at 5 V, bridging raises the power into an 8-Ω speaker from a  
    singled-ended (SE, ground reference) limit of 250 mW to 1 W. In sound power that is a 6-dB improvement —  
    which is loudness that can be heard. In addition to increased power there are frequency response concerns.  
    Consider the single-supply SE configuration shown in Figure 45. A coupling capacitor is required to block the  
    dc offset voltage from reaching the load. These capacitors can be quite large (approximately 33 µF to 1000 µF)  
    so they tend to be expensive, heavy, occupy valuable PCB area, and have the additional drawback of limiting  
    low-frequency performance of the system. This frequency limiting effect is due to the high pass filter network  
    created with the speaker impedance and the coupling capacitance and is calculated with equation 6.  
    1
    (6)  
    f
    c
    2 R C  
    L
    C
    For example, a 68-µF capacitor with an 8-Ω speaker would attenuate low frequencies below 293 Hz. The BTL  
    configuration cancels the dc offsets, which eliminates the need for the blocking capacitors. Low-frequency  
    performance is then limited only by the input network and speaker response. Cost and PCB space are also  
    minimized by eliminating the bulky coupling capacitor.  
    V
    DD  
    –3 dB  
    V
    O(PP)  
    C
    C
    V
    O(PP)  
    R
    L
    f
    c
    Figure 45. Single-Ended Configuration and Frequency Response  
    25  
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    SLOS284 – NOVEMBER 1999  
    APPLICATION INFORMATION  
    Increasing power to the load does carry a penalty of increased internal power dissipation. The increased  
    dissipation is understandable considering that the BTL configuration produces 4× the output power of the SE  
    configuration. Internal dissipation versus output power is discussed further in the crest factor and thermal  
    considerations section.  
    single-ended operation  
    In SE mode (see Figure 44 and Figure 45), the load is driven from the primary amplifier output for each channel  
    (OUT+, terminals 21 and 4).  
    The amplifier switches single-ended operation when the SE/BTL terminal is held high. This puts the negative  
    outputs in a high-impedance state, and reduces the amplifier’s gain to 1 V/V.  
    input MUX operation  
    The input MUX allows two separate inputs to be applied to the amplifier. This allows the designer to choose  
    which input is active independent of the state of the SE/BTL terminal. When the HP/LINE terminal is held high,  
    the headphone inputs are active. When the HP/LINE terminal is held low, the line BTL inputs are active.  
    BTL amplifier efficiency  
    Class-AB amplifiers are notoriously inefficient. The primary cause of these inefficiencies is voltage drop across  
    the output stage transistors. There are two components of the internal voltage drop. One is the headroom or  
    dc voltage drop that varies inversely to output power. The second component is due to the sinewave nature of  
    the output. The total voltage drop can be calculated by subtracting the RMS value of the output voltage from  
    V
    .TheinternalvoltagedropmultipliedbytheRMSvalueofthesupplycurrent,I rms,determinestheinternal  
    DD  
    DD  
    power dissipation of the amplifier.  
    An easy-to-use equation to calculate efficiency starts out as being equal to the ratio of power from the power  
    supply to the power delivered to the load. To accurately calculate the RMS and average values of power in the  
    load and in the amplifier, the current and voltage waveform shapes must first be understood (see Figure 46).  
    I
    V
    O
    DD  
    I
    DD(avg)  
    V
    (LRMS)  
    Figure 46. Voltage and Current Waveforms for BTL Amplifiers  
    Although the voltages and currents for SE and BTL are sinusoidal in the load, currents from the supply are very  
    different between SE and BTL configurations. In an SE application the current waveform is a half-wave rectified  
    shape, whereas in BTL it is a full-wave rectified waveform. This means RMS conversion factors are different.  
    Keep in mind that for most of the waveform both the push and pull transistors are not on at the same time, which  
    supports the fact that each amplifier in the BTL device only draws current from the supply for half the waveform.  
    The following equations are the basis for calculating amplifier efficiency.  
    26  
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    APPLICATION INFORMATION  
    P
    L
    Efficiency of a BTL amplifier  
    Where:  
    (7)  
    P
    SUP  
    2
    L
    2
    V rms  
    V
    V
    P
    2R  
    L
    P
    P
    , andV  
    , therefore, P  
    L
    L
    LRMS  
    R
    2
    L
    2V  
    V
    V
    P
    1
    P
    1
    P
    [cos(t)]  
    P
    V
    I
    avg  
    P
    I
    avg  
    DD  
    sin(t) dt  
    and  
    and  
    0
    SUP  
    DD DD  
    R
    L
    R
    R
    L
    L
    0
    Therefore,  
    2 V  
    V
    DD  
    R
    P
    SUP  
    L
    substituting P and P  
    into equation 7,  
    L
    SUP  
    2
    V
    P
    P = Power devilered to load  
    L
    SUP  
    LRMS  
    P
    V
    = Power drawn from power supply  
    = RMS voltage on BTL load  
    2 R  
    V
    L
    P
    Efficiency of a BTL amplifier  
    Where:  
    4 V  
    2 V  
    V
    P
    DD  
    DD  
    R
    R = Load resistance  
    L
    V = Peak voltage on BTL load  
    P
    L
    I
    avg = Average current drawn from  
    the power supply  
    DD  
    V
    2 P R  
    L L  
    V
    = Power supply voltage  
    = Efficiency of a BTL amplifier  
    P
    DD  
    η
    BTL  
    Therefore,  
    2 P  
    R
    L
    L
    (8)  
    BTL  
    4 V  
    DD  
    Table 3 employs equation 8 to calculate efficiencies for four different output power levels. Note that the efficiency  
    of the amplifier is quite low for lower power levels and rises sharply as power to the load is increased resulting  
    in a nearly flat internal power dissipation over the normal operating range. Note that the internal dissipation at  
    full output power is less than in the half power range. Calculating the efficiency for a specific system is the key  
    to proper power supply design. For a stereo 1-W audio system with 8-Ω loads and a 5-V supply, the maximum  
    draw on the power supply is almost 3.25 W.  
    Table 3. Efficiency Vs Output Power in 5-V 8-Ω BTL Systems  
    Output Power  
    (W)  
    Efficiency  
    (%)  
    Peak Voltage  
    (V)  
    Internal Dissipation  
    (W)  
    0.25  
    0.50  
    1.00  
    1.25  
    31.4  
    44.4  
    62.8  
    70.2  
    2.00  
    2.83  
    4.00  
    0.55  
    0.62  
    0.59  
    0.53  
    †
    4.47  
    †
    High peak voltages cause the THD to increase.  
    A final point to remember about Class-AB amplifiers (either SE or BTL) is how to manipulate the terms in the  
    efficiency equation to utmost advantage when possible. Note that in equation 8, V is in the denominator. This  
    DD  
    indicates that as V  
    goes down, efficiency goes up.  
    DD  
    27  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
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    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    APPLICATION INFORMATION  
    crest factor and thermal considerations  
    Class-AB power amplifiers dissipate a significant amount of heat in the package under normal operating  
    conditions. AtypicalmusicCDrequires12dBto15dBofdynamicrange, orheadroomabovetheaveragepower  
    output, to pass the loudest portions of the signal without distortion. In other words, music typically has a crest  
    factor between 12 dB and 15 dB. When determining the optimal ambient operating temperature, the internal  
    dissipated power at the average output power level must be used. From the TPA0212 data sheet, one can see  
    that when the TPA0212 is operating from a 5-V supply into a 3-Ω speaker 4-W peaks are available. Converting  
    watts to dB:  
    P
    W
    4 W  
    1 W  
    P
    10Log  
    10Log  
    6 dB  
    (9)  
    dB  
    P
    ref  
    Subtracting the headroom restriction to obtain the average listening level without distortion yields:  
    6 dB – 15 dB = –9 dB (15 dB crest factor)  
    6 dB – 12 dB = –6 dB (12 dB crest factor)  
    6 dB – 9 dB = –3 dB (9 dB crest factor)  
    6 dB – 6 dB = 0 dB (6 dB crest factor)  
    6 dB – 3 dB = 3 dB (3 dB crest factor)  
    Converting dB back into watts:  
    PdB 10  
    P
    10  
    P
    W
    ref  
    (10)  
    63 mW (18 dB crest factor)  
    125 mW (15 dB crest factor)  
    250 mW (9 dB crest factor)  
    500 mW (6 dB crest factor)  
    1000 mW (3 dB crest factor)  
    2000 mW (15 dB crest factor)  
    This is valuable information to consider when attempting to estimate the heat dissipation requirements for the  
    amplifier system. Comparing the absolute worst case, which is 2 W of continuous power output with a 3 dB crest  
    factor, against 12 dB and 15 dB applications drastically affects maximum ambient temperature ratings for the  
    system. Using the power dissipation curves for a 5-V, 3-Ω system, the internal dissipation in the TPA0212 and  
    maximum ambient temperatures is shown in Table 4.  
    Table 4. TPA0212 Power Rating, 5-V, 3-Ω, Stereo  
    PEAK OUTPUT POWER  
    (W)  
    POWER DISSIPATION  
    (W/Channel)  
    MAXIMUM AMBIENT  
    TEMPERATURE  
    AVERAGE OUTPUT POWER  
    4
    4
    4
    4
    4
    4
    2 W (3 dB)  
    1.7  
    1.6  
    1.4  
    1.1  
    0.8  
    0.6  
    –3°C  
    6°C  
    1000 mW (6 dB)  
    500 mW (9 dB)  
    250 mW (12 dB)  
    125 mW (15 dB)  
    63 mW (18 dB)  
    24°C  
    51°C  
    78°C  
    96°C  
    28  
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    APPLICATION INFORMATION  
    crest factor and thermal considerations (continued)  
    Table 5. TPA0212 Power Rating, 5-V, 8-Ω, Stereo  
    POWER DISSIPATION  
    AVERAGE OUTPUT POWER  
    MAXIMUM AMBIENT  
    TEMPERATURE  
    PEAK OUTPUT POWER  
    (W/Channel)  
    2.5 W  
    2.5 W  
    2.5 W  
    2.5 W  
    1250 mW (3 dB crest factor)  
    1000 mW (4 dB crest factor)  
    500 mW (7 dB crest factor)  
    250 mW (10 dB crest factor)  
    0.55  
    0.62  
    0.59  
    0.53  
    100°C  
    94°C  
    97°C  
    102°C  
    The maximum dissipated power, P  
    a 3-Ω load. As a result, this simple formula for calculating P  
    , is reached at a much lower output power level for an 8-Ω load than for  
    Dmax  
    may be used for an 8-Ω application:  
    Dmax  
    2
    2V  
    DD  
    (11)  
    P
    Dmax  
    2
    R
    L
    However, in the case of a 3-Ω load, the P  
    The amplifier may therefore be operated at a higher ambient temperature than required by the P  
    for a 3-Ω load.  
    occurs at a point well above the normal operating power level.  
    Dmax  
    formula  
    Dmax  
    The maximum ambient temperature depends on the heat sinking ability of the PCB system. The derating factor  
    for the PWP package is shown in the dissipation rating table (see page 4). Converting this to Θ  
    :
    JA  
    1
    1
    Θ
    45°C W  
    (12)  
    JA  
    0.022  
    Derating Factor  
    To calculate maximum ambient temperatures, first consider that the numbers from the dissipation graphs are  
    per channel so the dissipated power needs to be doubled for two channel operation. Given Θ , the maximum  
    JA  
    allowable junction temperature, and the total internal dissipation, the maximum ambient temperature can be  
    calculated with the following equation. The maximum recommended junction temperature for the TPA0212 is  
    150°C. The internal dissipation figures are taken from the Power Dissipation vs Output Power graphs.  
    T
    Max  
    T Max  
    Θ
    P
    (13)  
    A
    J
    JA  
    D
    (
    )
    2
    (
    )
    150 45 0.6  
    96°C 15 dB crest factor  
    NOTE:  
    Internal dissipation of 0.6 W is estimated for a 2-W system with 15 dB crest factor per channel.  
    Tables 4 and 5 show that for some applications no airflow is required to keep junction temperatures in the  
    specified range. The TPA0212 is designed with thermal protection that turns the device off when the junction  
    temperature surpasses 150°C to prevent damage to the IC. Tables 4 and 5 were calculated for maximum  
    listening volume without distortion. When the output level is reduced the numbers in the table change  
    significantly. Also, using 8-Ω speakers dramatically increases the thermal performance by increasing amplifier  
    efficiency.  
    29  
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    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    APPLICATION INFORMATION  
    SE/BTL operation  
    The ability of the TPA0212 to easily switch between BTL and SE modes is one of its most important cost saving  
    features. This feature eliminates the requirement for an additional headphone amplifier in applications where  
    internal stereo speakers are driven in BTL mode but external headphone or speakers must be accommodated.  
    Internal to the TPA0212, two separate amplifiers drive OUT+ and OUT–. The SE/BTL input (terminal 15)  
    controls the operation of the follower amplifier that drives LOUT– and ROUT– (terminals 9 and 16). When  
    SE/BTLisheldlow, theamplifierisonandtheTPA0212isintheBTLmode. WhenSE/BTLisheldhigh, theOUT–  
    amplifiers are in a high output impedance state, which configures the TPA0212 as an SE driver from LOUT+  
    and ROUT+ (terminals 4 and 21). I  
    is reduced by approximately one-half in SE mode. Control of the SE/BTL  
    DD  
    input can be from a logic-level CMOS source or, more typically, from a resistor divider network as shown in  
    Figure 47.  
    RHPIN  
    20  
    R
    MUX  
    23 RLINEIN  
    –
    ROUT+ 21  
    +
    8
    RIN  
    C
    OUTR  
    V
    DD  
    330 µF  
    –
    ROUT– 16  
    SE/BTL 15  
    1 kΩ  
    +
    100 kΩ  
    100 kΩ  
    Figure 47. TPA0212 Resistor Divider Network Circuit  
    Using a readily available 1/8-in. (3.5 mm) stereo headphone jack, the control switch is closed when no plug is  
    inserted. When closed the 100-kΩ/1-kΩ divider pulls the SE/BTL input low. When a plug is inserted, the 1-kΩ  
    resistor is disconnected and the SE/BTL input is pulled high. When the input goes high, the OUT– amplifier is  
    shut down causing the speaker to mute (virtually open-circuits the speaker). The OUT+ amplifier then drives  
    through the output capacitor (C ) into the headphone jack.  
    O
    30  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    APPLICATION INFORMATION  
    PC BEEP operation  
    The PC BEEP input allows a system beep to be sent directly from a computer through the amplifier to the  
    speakerswithfewexternalcomponents. Theinputisactivatedautomatically. WhenthePCBEEPinputisactive,  
    both of the LINEIN and HPIN inputs are deselected and both the left and right channels are driven in BTL mode  
    with the signal from PC BEEP. The gain from the PC BEEP input to the speakers is fixed at 0.3 V/V and is  
    independent of the volume setting. When the PC BEEP input is deselected, the amplifier will return to the  
    previous operating mode and volume setting. Furthermore, if the amplifier is in shutdown mode, activating PC  
    BEEPwill take the device out of shutdown and output the PC BEEP signal, then return the amplifier to shutdown  
    mode.  
    The preferred input signal is a square wave or pulse train with an amplitude of 1 V or greater. To be accurately  
    pp  
    detected, the signal must have a minimum of 1 V amplitude, rise and fall times of less than 0.1 µs and a  
    pp  
    minimum of 8 rising edges. When the signal is no longer detected, the amplifier will return to its previous  
    operating mode and volume setting.  
    If it is desired to ac-couple the PC BEEP input, the value of the coupling capacitor should be chosen to satisfy  
    equation 14:  
    1
    C
    (14)  
    PCB  
    2 ƒ  
    (100 k )  
    PCB  
    ThePCBEEPinputcanalsobedc-coupledtoavoidusingthiscouplingcapacitor. Thepinnormallysitsatmidrail  
    when no signal is present.  
    shutdown modes  
    The TPA0212 employs a shutdown mode of operation designed to reduce supply current, I , to the absolute  
    DD  
    minimum level during periods of nonuse for battery-power conservation. The SHUTDOWN input terminal  
    should be held high during normal operation when the amplifier is in use. Pulling SHUTDOWN low causes the  
    outputs to mute and the amplifier to enter a low-current state, I  
    unconnected because amplifier operation would be unpredictable.  
    = 150 µA. SHUTDOWN should never be left  
    DD  
    Table 6. HP/LINE, SE/BTL, and Shutdown Functions  
    †
    AMPLIFIER STATE  
    INPUT OUTPUT  
    Mute  
    INPUTS  
    HP/LINE  
    X
    SE/BTL  
    X
    SHUTDOWN  
    Low  
    X
    Low  
    Low  
    High  
    Low  
    High  
    High  
    Line  
    Line  
    HP  
    BTL  
    SE  
    Low  
    High  
    High  
    High  
    High  
    BTL  
    SE  
    High  
    HP  
    †
    Inputs should never be left unconnected.  
    X = do not care  
    31  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    TPA0212  
    STEREO 2-W AUDIO POWER AMPLIFIER  
    WITH FOUR SELECTABLE GAIN SETTINGS AND MUX CONTROL  
    SLOS284 – NOVEMBER 1999  
    MECHANICAL DATA  
    PWP (R-PDSO-G**)  
    PowerPAD PLASTIC SMALL-OUTLINE PACKAGE  
    20-PIN SHOWN  
    0,30  
    0,19  
    0,65  
    20  
    M
    0,10  
    11  
    Thermal Pad  
    (See Note D)  
    0,15 NOM  
    4,50  
    4,30  
    6,60  
    6,20  
    Gage Plane  
    1
    10  
    0,25  
    A
    0°–8°  
    0,75  
    0,50  
    Seating Plane  
    0,10  
    0,15  
    0,05  
    1,20 MAX  
    PINS **  
    14  
    16  
    20  
    24  
    28  
    DIM  
    5,10  
    4,90  
    5,10  
    4,90  
    6,60  
    6,40  
    7,90  
    7,70  
    9,80  
    9,60  
    A MAX  
    A MIN  
    4073225/E 03/97  
    NOTES: A. All linear dimensions are in millimeters.  
    B. This drawing is subject to change without notice.  
    C. Body dimensions do not include mold flash or protrusions.  
    D. Thepackagethermalperformancemaybeenhancedbybondingthethermalpadtoanexternalthermalplane.Thispadiselectrically  
    and thermally connected to the backside of the die and terminals 1, 12, 13, and 24. The dimensions of the thermal pad are  
    2.40 mm × 4.70 mm (maximum). The pad is centered on the bottom of the package.  
    E. Falls within JEDEC MO-153  
    PowerPAD is a trademark of Texas Instruments Incorporated.  
    32  
    POST OFFICE BOX 655303 • DALLAS, TEXAS 75265  
    IMPORTANT NOTICE  
    Texas Instruments and its subsidiaries (TI) reserve the right to make changes to their products or to discontinue  
    any product or service without notice, and advise customers to obtain the latest version of relevant information  
    to verify, before placing orders, that information being relied on is current and complete. All products are sold  
    subject to the terms and conditions of sale supplied at the time of order acknowledgement, including those  
    pertaining to warranty, patent infringement, and limitation of liability.  
    TI warrants performance of its semiconductor products to the specifications applicable at the time of sale in  
    accordance with TI’s standard warranty. Testing and other quality control techniques are utilized to the extent  
    TI deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily  
    performed, except those mandated by government requirements.  
    CERTAIN APPLICATIONS USING SEMICONDUCTOR PRODUCTS MAY INVOLVE POTENTIAL RISKS OF  
    DEATH, PERSONAL INJURY, OR SEVERE PROPERTY OR ENVIRONMENTAL DAMAGE (“CRITICAL  
    APPLICATIONS”). TI SEMICONDUCTOR PRODUCTS ARE NOT DESIGNED, AUTHORIZED, OR  
    WARRANTED TO BE SUITABLE FOR USE IN LIFE-SUPPORT DEVICES OR SYSTEMS OR OTHER  
    CRITICAL APPLICATIONS. INCLUSION OF TI PRODUCTS IN SUCH APPLICATIONS IS UNDERSTOOD TO  
    BE FULLY AT THE CUSTOMER’S RISK.  
    In order to minimize risks associated with the customer’s applications, adequate design and operating  
    safeguards must be provided by the customer to minimize inherent or procedural hazards.  
    TI assumes no liability for applications assistance or customer product design. TI does not warrant or represent  
    that any license, either express or implied, is granted under any patent right, copyright, mask work right, or other  
    intellectual property right of TI covering or relating to any combination, machine, or process in which such  
    semiconductor products or services might be or are used. TI’s publication of information regarding any third  
    party’s products or services does not constitute TI’s approval, warranty or endorsement thereof.  
    Copyright 1999, Texas Instruments Incorporated  
    配单直通车
    TPA0212PWP产品参数
    型号:TPA0212PWP
    Brand Name：Texas Instruments
    是否无铅： 不含铅
    是否Rohs认证： 符合
    生命周期：Active
    IHS 制造商：TEXAS INSTRUMENTS INC
    零件包装代码：TSSOP
    包装说明：POWERPAD, PLASTIC, HTSSOP-24
    针数：24
    Reach Compliance Code：compliant
    ECCN代码：EAR99
    HTS代码：8542.39.00.01
    Factory Lead Time：1 week
    风险等级：5.13
    Samacsys Confidence：3
    Samacsys Status：Released
    Samacsys PartID：320842
    Samacsys Pin Count：25
    Samacsys Part Category：Integrated Circuit
    Samacsys Package Category：Small Outline Packages
    Samacsys Footprint Name：TSSOP
    Samacsys Released Date：2020-04-14 11:33:52
    Is Samacsys：N
    商用集成电路类型：VOLUME CONTROL CIRCUIT
    谐波失真：1%
    JESD-30 代码：R-PDSO-G24
    JESD-609代码：e4
    长度：7.8 mm
    湿度敏感等级：2
    信道数量：2
    功能数量：1
    端子数量：24
    最高工作温度：85 °C
    最低工作温度：-40 °C
    标称输出功率：2 W
    封装主体材料：PLASTIC/EPOXY
    封装代码：HTSSOP
    封装等效代码：TSSOP24,.25
    封装形状：RECTANGULAR
    封装形式：SMALL OUTLINE, HEAT SINK/SLUG, THIN PROFILE, SHRINK PITCH
    峰值回流温度（摄氏度）：260
    电源：5 V
    认证状态：Not Qualified
    座面最大高度：1.2 mm
    子类别：Audio/Video Amplifiers
    最大压摆率：8 mA
    最大供电电压 (Vsup)：5.5 V
    最小供电电压 (Vsup)：4.5 V
    表面贴装：YES
    技术：CMOS
    温度等级：INDUSTRIAL
    端子面层：Nickel/Palladium/Gold (Ni/Pd/Au)
    端子形式：GULL WING
    端子节距：0.65 mm
    端子位置：DUAL
    处于峰值回流温度下的最长时间：NOT SPECIFIED
    宽度：4.4 mm
    Base Number Matches：1
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