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TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

DGQ PACKAGE

(TOP VIEW)

D

Ideal for Notebook Computers, PDAs, and

Other Small Portable Audio Devices

D

2 W Into 4 Ω From 5-V Supply

0.6 W Into 4 Ω From 3-V Supply

Stereo Head Phone Drive

1

2

3

4

5

FILT_CAP

SHUTDOWN

LO/MO–

LIN

GND

ST/MN

RO/MO+

10

9

V

8

DD

BYPASS

7

Mono (BTL) Signal Created by Summing

Left and Right Signals

RIN

6

D

Wide Power Supply Compatibility

3 V to 5 V

D

Meets PC99 Portable Specs (target)

D

Low Supply Current

– 4 mA Typical at 5 V

– 3.3 mA Typical at 3 V

D

Shutdown Control . . . 1 µA Typical

Shutdown Pin is TTL Compatible

–40°C to 85°C Operating Temperature

Range

D

Space-Saving, Thermally-Enhanced MSOP

Packaging

description

The TPA0233 is a 2-W mono bridge-tied-load (BTL) amplifier designed to drive speakers with as low as 4-Ω

impedance. The mono signal is created by summing left and right inputs. The amplifier can be reconfigured on

the fly to drive two stereo single-ended (SE) signals into head phones. This makes the device ideal for use in

small notebook computers, PDAs, digital personal audio players, anyplace a mono speaker and stereo

headphones are required. From a 5-V supply, the TPA0233 deliver 2 W of power into a 4-Ω speaker.

The gain of the input stage is set by the user-selected input resistor and a 50-kΩ internal feedback resistor

(A = – R / R ). The power stage is internally configured with a gain of –1.25 V/V in SE mode, and –2.5 V/V in

V

F

I

BTL mode. Thus, the overall gain of the amplifier is 62.5 kΩ/ R in SE mode and 125 kΩ/ R in BTL mode. The

I

input terminals are high-impedance CMOS inputs, and can be used as summing nodes.

The TPA0233 is available in the 10-pin thermally-enhanced MSOP package (DGQ) and operates over an

ambient temperature range of –40°C to 85°C.

Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of

Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.

PRODUCTION DATA information is current as of publication date.

Products conform to specifications per the terms of Texas Instruments

standard warranty. Production processing does not necessarily include

testing of all parameters.

1

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

functional block diagram

C

B

4

BYPASS

V

DD

V

DD

3

1

GND

8

FILT_CAP

V

DD

BYPASS

1 µF

50 kΩ

1.25*R

100 kΩ

5

RIN

R

M

U

X

C

–

Right

Audio

Input

RO/MO+

6

+

C

I

+

R

I

BYPASS

100 kΩ

50 kΩ

ST/MN

7

Stereo/Mono

Control

1.25*R

Left

Audio

Input

R

M

U

X

C

I

C

–

R

I

–

9

2

LIN

LO/MO– 10

+

1 kΩ

BYPASS

From

System Control

Shutdown

and Depop

Circuitry

SHUTDOWN

AVAILABLE OPTIONS

PACKAGED DEVICES

MSOP

SYMBOLIZATION

†

T

A

MSOP

(DGQ)

–40°C to 85°C

TPA0233DGQ

AEJ

†

The DGQ package are available taped and reeled. To order a taped and reeled part, add the

suffix R to the part number (e.g., TPA0233DGQR).

2

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

Terminal Functions

TERMINAL

NAME

BYPASS

I/O

DESCRIPTION

NO.

4

I

BYPASS is the tap to the voltage divider for internal mid-supply bias. This terminal should be connected

to a 0.1-µF to 1-µF capacitor.

FILT_CAP

GND

1

8

I

Terminal is used to filter supply.

Ground terminal

LIN

9

I

Left-channel input terminal

LO/MO–

RIN

10

5

O

I

Left-output in SE mode and mono negative output in BTL mode.

Right-channel input terminal

RO/MO+

SHUTDOWN

ST/MN

6

O

I

Right-output in SE mode and mono positive output in BTL mode

SHUTDOWN places the entire device in shutdown mode when held low. TTL compatible input.

2

7

I

Selects between stereo and mono mode. When held high, the amplifier is in SE stereo mode, while held

low, the amplifier is in BTL mono mode.

V

DD

3

I

V

DD

is the supply voltage terminal.

†

absolute maximum ratings over operating free-air temperature range (unless otherwise noted)

Supply voltage, V

. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 V

DD

Input voltage range, V . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to V +0.3 V

I

DD

Continuous total power dissipation . . . . . . . . . . . . . . . . . . . . . internally limited (see Dissipation Rating Table)

Operating free-air temperature range, T (see Table 3) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to 85°C

A

Operating junction temperature range, T . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to 150°C

J

Storage temperature range, T

. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –65°C to 150°C

stg

Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 260°C

Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and

functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not

implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.

†

DISSIPATION RATING TABLE

PACKAGE

T

A

≤ 25°C

DERATING FACTOR

T

A

= 70°C

T = 85°C

A

‡

DGQ

2.14 W

17.1 mW/°C

1.37 W

1.11 W

‡

See the Texas Instruments document, PowerPAD Thermally Enhanced Package Application Report

(SLMA002), for more information on the PowerPAD package. The thermal data was measured on a PCB

layoutbased on theinformation inthe section entitledTexasInstrumentsRecommendedBoardforPowerPAD

on page 33 of that document.

recommended operating conditions

MIN

2.5

2.7

4.5

2

MAX

UNIT

Supply voltage, V

DD

5.5

V

= 3 V

= 5 V

DD

ST/MN

High-level input voltage, V

V

DD

IH

SHUTDOWN

V

= 3 V

= 5 V

1.65

2.75

0.8

DD

ST/MN

Low-level input voltage, V

V

DD

IL

SHUTDOWN

Operating free-air temperature, T

–40

85

°C

A

PowerPAD is a trademark of Texas Instruments.

3

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

electrical characteristics at specified free-air temperature, V

noted)

= 3 V, T = 25°C (unless otherwise

A

DD

PARAMETER

TEST CONDITIONS

MIN

TYP

MAX

30

5

UNIT

mV

mA

µA

|V

|

Output offset voltage (measured differentially) SHUTDOWN = 2 V, ST/MN = 0, R = 4 Ω

OO

L

I

Supply current

V

2.5 V, SHUTDOWN = 2 V

3.3

1

DD

DD(SD)

DD

SHUTDOWN = 0 V

SHUTDOWN, V

I

Supply current, shutdown mode

10

1

= 3.3 V,

V = 3.3 V

I

DD

= 3.3 V,

|I

|

High-level input current

µA

IH

ST/MN, V

V = 3.3 V

1

DD

SHUTDOWN, V

I

= 3.3 V,

V = 0 V

1

DD

= 3.3 V,

I

|

Low-level input current

Feedback resistor

µA

kΩ

IL

ST/MN, V

V = 0 V

1

DD

I

V

DD

= 2.5 V, R = 4 Ω, SHUTDOWN = 2 V,

L

R

47

50

57

F

ST/MN = 1.375 V

operating characteristics, V

= 3 V, T = 25°C, R = 4 Ω

A L

DD

PARAMETER

TEST CONDITIONS

MIN

TYP MAX

UNIT

THD = 1%,

BTL mode

SE mode,

660

33

P

O

Output power, See Note 1

mW

THD = 0.1%,

R = 32 Ω

L

THD + N Total harmonic distortion plus noise

Maximum output power bandwidth

P

= 500 mW, f = 20 Hz to 20 kHz

0.3%

20

O

B

OM

Gain = 2,

THD = 2%

kHz

NOTE 1: Output power is measured at the output terminals of the device at f = 1 kHz.

electrical characteristics at specified free-air temperature, V

noted)

= 5 V, T = 25°C (unless otherwise

A

DD

PARAMETER

TEST CONDITIONS

MIN

TYP

MAX

30

UNIT

mV

mA

µA

|V

|

Output offset voltage (measured differentially) SHUTDOWN = 2 V, ST/MN = 0, R = 4 Ω

OO

L

I

Supply current

SHUTDOWN = 2 V

SHUTDOWN = 0 V

4

1

7

DD

Supply current, shutdown mode

10

DD(SD)

SHUTDOWN, V

= 5.5 V,

V = 5.5 V

1

DD

= 5.5 V,

I

|I

|

High-level input current

Low-level input current

µA

IH

ST/MN, V

V = 5.5 V

I

DD

SHUTDOWN, V

= 5.5 V,

V = 0 V

I

DD

= 5.5 V,

|

IL

ST/MN, V

V = 0 V

I

DD

operating characteristics, V

= 5 V, T = 25°C, R = 4 Ω

DD

A

L

PARAMETER

TEST CONDITIONS

MIN

TYP

2

MAX

UNIT

W

THD = 1%,

THD = 0.1%,

= 1 W,

BTL mode

SE mode,

P

Output power, see Note 1

O

R

= 32 Ω

92

mW

L

THD + N Total harmonic distortion plus noise

Maximum output power bandwidth

P

O

f = 20 Hz to 20 kHz

THD = 2%

0.2%

20

B

OM

Gain = 2.5,

kHz

NOTE 1: Output power is measured at the output terminals of the device at f = 1 kHz.

4

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

TYPICAL CHARACTERISTICS

Table of Graphs

FIGURE

Supply ripple rejection ratio

Supply current

vs Frequency

1, 2

I

vs Supply voltage

vs Load resistance

vs Frequency

3

4, 5

DD

P

Output power

O

6, 7

8, 9, 10, 11

12, 13, 14, 15, 16, 17

18, 19

THD+N

Total harmonic distortion plus noise

vs Output power

vs Frequency

V

Output noise voltage

Closed loop response

Crosstalk

n

20, 21

vs Frequency

22, 23

SUPPLY RIPPLE REJECTION RATIO

vs

FREQUENCY

0

–10

–20

0

–10

–20

R

C

= 8 Ω

= 1 µF

L

B

R

C

= 32 Ω

= 1 µF

L

B

Mode = Mono

Mode = Stereo

–30

–40

–50

–60

–70

–80

–30

–40

–50

–60

–70

–80

–90

–100

20

100

1k

10k 20k

20

100

1k

10k 20k

f – Frequency – Hz

Figure 1

Figure 2

5

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

TYPICAL CHARACTERISTICS

SUPPLY CURRENT

vs

OUTPUT POWER

vs

SUPPLY VOLTAGE

6

5

4

3

2

1

0

3.0

2.5

2.0

1.5

1.0

0.5

0.0

THD+N = 1%

f = 1 kHz

Mode = Mono

A

V

= 8 dB

T

= 25 °C

A

R

= 4 Ω

L

R

= 8 Ω

L

Bypass = V /2 VDC

DD

V

From Low-to-High Level

DD

Mode = Stereo

R

= Open

L

2.5

3.0

3.5

4.0

4.5

5.0

5.5

3.0

3.5

4.0

4.5

5.0

5.5

V

DD

– Supply Voltage – V

V

DD

– Supply Voltage – V

Figure 3

Figure 4

OUTPUT POWER

vs

OUTPUT POWER

vs

LOAD RESISTANCE

SUPPLY VOLTAGE

2.5

500

400

300

200

100

0

THD+N = 1%

f = 1 kHz

THD+N = 1%

f = 1 kHz

Mode = Mono

Mode = Stereo

= 2 dB

2.0

1.5

1.0

0.5

0.0

A

V

A

V

= 8 dB

R

= 8 Ω

L

V

DD

= 5 V

R

= 32 Ω

L

V

= 3 V

R

DD

0

10

20

30

40

50

60

3.0

3.5

4.0

4.5

5.0

5.5

– Load Resistance – Ω

V

DD

– Supply Voltage – V

L

Figure 5

Figure 6

6

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

TYPICAL CHARACTERISTICS

OUTPUT POWER

vs

LOAD RESISTANCE

700

600

500

400

300

200

100

0

THD+N = 1%

f = 1 kHz

Mode = Stereo

A

V

= 2 dB

V

= 5 V

DD

V

= 3 V

DD

0

10

20

30

40

50

60

R

– Load Resistance – Ω

L

Figure 7

TOTAL HARMONIC DISTORTION PLUS NOISE

vs

FREQUENCY

1

V

P

R

= 3 V

= 250 mW

= 8 Ω

DD

O

L

V

= 5 V

DD

P

R

= 1 W

O

= 8 Ω

L

Mode = Mono

0.1

A

V

= 20 dB

A = 20 dB

V

A

V

= 8 dB

0.01

0.001

0.01

0.001

A

V

= 8 dB

20

100

1k

10k 20k

20

100

1k

10k 20k

f – Frequency – Hz

Figure 8

Figure 9

7

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

TYPICAL CHARACTERISTICS

TOTAL HARMONIC DISTORTION PLUS NOISE

vs

FREQUENCY

1

V

P

R

= 3 V

= 25 mW

= 32 Ω

DD

O

L

V

= 5 V

DD

P

R

= 75 mW

O

= 32 Ω

L

Mode = Stereo

0.1

A

= 14 dB

= 2 dB

100

V

A

= 14 dB

V

0.01

0.001

0.01

0.001

A

V

A

V

= 2 dB

20

1k

10k 20k

20

100

1k

10k 20k

f – Frequency – Hz

Figure 10

Figure 11

TOTAL HARMONIC DISTORTION PLUS NOISE

vs

OUTPUT POWER

10

V

R

= 3 V

DD

= 4 Ω

V

R

= 3 V

DD

= 8 Ω

L

Mode = Mono

= 2.5 dB

Mode = Mono

A

V

A

V

= 2.5 dB

20 kHz

1

15 kHz

1 kHz

20 Hz

0.1

0.01

0.1

0.01

1 kHz

20 Hz

0.01

0.1

1

0.01

0.1

1

P

O

– Output Power – W

P

O

– Output Power – W

Figure 12

Figure 13

8

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

TYPICAL CHARACTERISTICS

TOTAL HARMONIC DISTORTION PLUS NOISE

vs

OUTPUT POWER

10

V

R

= 5 V

V

R

= 3 V

= 32 Ω

DD

= 4 Ω

DD

L

Mode = Mono

= 2.5 dB

Mode = Stereo

= 1.25 dB

A

V

20 kHz

1

15 kHz

1 kHz

20 kHz

0.1

0.01

0.1

0.01

15 kHz

1 kHz

20 Hz

0.01

0.1

0.01

0.1

1

10

P

O

– Output Power – W

P

– Output Power – W

O

Figure 14

Figure 15

TOTAL HARMONIC DISTORTION PLUS NOISE

vs

OUTPUT POWER

10

V

R

= 5 V

DD

= 8 Ω

V

R

= 5 V

= 32 Ω

DD

L

Mode = Mono

= 2.5 dB

Mode = Stereo

= 1.25 dB

A

V

A

V

1

20 kHz

1 kHz

15 kHz

0.1

0.01

0.1

0.01

20 kHz

15 kHz

20 Hz

0.1

1 kHz

0.01

0.1

1

0.01

1

10

P

O

– Output Power – W

P

O

– Output Power – W

Figure 16

Figure 17

9

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

TYPICAL CHARACTERISTICS

OUTPUT NOISE VOLTAGE

vs

FREQUENCY

1k

100

10

1k

V

R

= 5 V

DD

= 8 Ω

V

R

= 5 V

DD

= 32 Ω

L

Mode = Mono

= 2.5 dB

Mode = Stereo

= 2 dB

A

V

A

V

100

10

1

20

100

1k

10k 20k

20

100

1k

10k 20k

f – Frequency – Hz

Figure 18

Figure 19

CLOSED LOOP RESPONSE

30

180°

135°

90°

V

R

= 5 V

DD

= 4 Ω

L

20

Mode = Mono

= 8 dB

A

Gain

V

10

0

45°

0°

Phase

–10

–20

–30

–45°

–90°

–40

–50

–135°

–180°

10

100

1k

10k

100k

1M

f – Frequency – Hz

Figure 20

10

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

TYPICAL CHARACTERISTICS

CLOSED LOOP RESPONSE

30

20

180°

135°

90°

V

R

= 5 V

DD

= 32 Ω

L

Mode = Stereo

= 2 dB

A

V

10

0

Gain

45°

0°

Phase

–10

–20

–30

–45°

–90°

–40

–50

–135°

–180°

10

100

1k

10k

100k

1M

f – Frequency – Hz

Figure 21

CROSSTALK

vs

FREQUENCY

CROSSTALK

vs

FREQUENCY

–50

–60

–50

Left-to-Right

V

R

= 5 V

= 32 Ω

= 75 mW

= 1.25 dB

DD

L

V

R

= 3 V

= 32 Ω

= 35 mW

= 1.25 dB

DD

L

–60

–70

P

O

P

O

A

V

A

V

–70

–80

–90

–100

–110

–100

–110

20

100

1k

10k 20k

20

100

1k

f – Frequency – Hz

Figure 23

10k 20k

f – Frequency – Hz

Figure 22

11

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

APPLICATION INFORMATION

gain setting via input resistance

The gain of the input stage is set by the user-selected input resistor and a 50-kΩ internal feedback resistor.

However, the power stage is internally configured with a gain of –1.25 V/V in stereo mode, and –2.5 V/V in mono

mode. Thus, the feedback resistor (R ) is effectively 62.5 kΩ in stereo mode and 125 kΩ in mono mode.

F

Therefore, the overall gain can be calculated using equations (1) and (2) stereo.

–125 kW

A

+

(Mono)

V

R

(1)

(2)

I

–62.5 kW

(Stereo)

R

I

The –3 dB frequency can be calculated using equation 3.

1

(3)

ƒ

+

–3 dB

2p R C

I i

If the filter must be more accurate, the value of the capacitor should be increased while the value of the resistor

to ground should be decreased. In addition, the order of the filter could be increased.

input capacitor, C

i

In the typical application an input capacitor (C ), is required to allow the amplifier to bias the input signal to the

i

proper dc level for optimum operation. In this case, C and the input resistance of the amplifier, R , form a

i

I

high-pass filter with the corner frequency determined in equation 4.

–3 dB

(4)

1

f

+

c(highpass)

2pR C

i

I

f

c

The value of C is important to consider as it directly affects the bass (low frequency) performance of the circuit.

i

Consider the example where R is 10 kΩ and the specification calls for a flat bass response down to 40 Hz.

I

Equation 2 is reconfigured as equation 5.

1

C +

i

2pR f

(5)

c

I

In this example, C is 0.4 µF so one would likely choose a value in the range of 0.47 µF to 1 µF. A further

I

consideration for this capacitor is the leakage path from the input source through the input network (C ) and the

i

feedback network to the load. This leakage current creates a dc offset voltage at the input to the amplifier that

reduces useful headroom, especially in high gain applications. For this reason a low-leakage tantalum or

ceramic capacitor is the best choice. When polarized capacitors are used, the positive side of the capacitor

should face the amplifier input in most applications as the dc level there is held at V /2, which is likely higher

DD

than the source dc level. Note that it is important to confirm the capacitor polarity in the application.

12

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

APPLICATION INFORMATION

power supply decoupling, C

(S)

The TPA0233 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling

to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also

prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is

achieved by using two capacitors of different types that target different types of noise on the power supply leads.

For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance

(ESR) ceramic capacitor, typically 0.1 µF placed as close as possible to the device V

filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 µF or greater placed near

lead, works best. For

DD

the audio power amplifier is recommended.

midrail bypass capacitor, C

(BYP)

The midrail bypass capacitor (C

During start-up or recovery from shutdown mode, C

), is the most critical capacitor and serves several important functions.

(BYP)

determines the rate at which the amplifier starts up.

(BYP)

The second function is to reduce noise produced by the power supply caused by coupling into the output drive

signal. This noise is from the midrail generation circuit internal to the amplifier, which appears as degraded

PSRR and THD+N.

Bypass capacitor (C

recommended for the best THD and noise performance.

), values of 0.47-µF to 1-µF ceramic or tantalum low-ESR capacitors are

(BYP)

output coupling capacitor, C

(C)

In the typical single-supply stereo configuration, an output coupling capacitor (C ) is required to block the dc

(C)

bias at the output of the amplifier, thus preventing dc currents in the load. As with the input coupling capacitor,

the output coupling capacitor and impedance of the load form a high-pass filter governed by equation 6.

–3 dB

1

f

+

(6)

c(high)

2pR C

L

(C)

f

c

Themaindisadvantage, fromaperformancestandpoint, istheloadimpedancesaretypicallysmall, whichdrives

the low-frequency corner higher, degrading the bass response. Large values of C are required to pass low

(C)

frequencies into the load. Consider the example where a C

of 330 µF is chosen and loads vary from 3 Ω,

(C)

4 Ω, 8 Ω, 32 Ω, 10 kΩ, to 47 kΩ. Table 1 summarizes the frequency response characteristics of each

configuration.

Table 1. Common Load Impedances vs Low Frequency Output Characteristics in Stereo (SE) Mode

R

C

Lowest Frequency

161 Hz

L

(C)

3 Ω

330 µF

4 Ω

8 Ω

120 Hz

60 Hz

32 Ω

10,000 Ω

47,000 Ω

Ą15 Hz

0.05 Hz

330 µF

0.01 Hz

13

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

APPLICATION INFORMATION

(continued)

output coupling capacitor, C

(C)

As Table 1 indicates, most of the bass response is attenuated into a 4-Ω load, an 8-Ω load is adequate,

headphone response is good, and drive into line level inputs (a home stereo for example) is exceptional.

Furthermore, the total amount of ripple current that must flow through the capacitor must be considered when

choosing the component. As shown in the application circuit, one coupling capacitor must be in series with the

mono loudspeaker for proper operation of the stereo-mono switching circuit. For a 4-Ω load, this capacitor must

be able to handle about 700 mA of ripple current for a continuous output power of 2 W.

using low-ESR capacitors

Low-ESR capacitors are recommended throughout this applications section. A real (as opposed to ideal)

capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this

resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this

resistance the more the real capacitor behaves like an ideal capacitor.

bridged-tied load versus single-ended mode

Figure 24 shows a Class-AB audio power amplifier (APA) in a BTL configuration. The TPA0233 BTL amplifier

consists of two Class-AB amplifiers driving both ends of the load. There are several potential benefits to this

differential drive configuration, but initially consider power to the load. The differential drive to the speaker

means that as one side is slewing up, the other side is slewing down, and vice versa. This, in effect, doubles

the voltage swing on the load as compared to a ground referenced load. Plugging 2 × V

equation, where voltage is squared, yields 4× the output power from the same supply rail and load impedance.

into the power

O(PP)

See equation 7.

V

O(PP)

(7)

V

+

(RMS)

Ǹ

2 2

2

V

(RMS)

Power +

R

L

V

DD

V

O(PP)

2x V

R

O(PP)

L

V

DD

–V

O(PP)

Figure 24. Bridge-Tied Load Configuration

14

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

APPLICATION INFORMATION

bridged-tied load versus single-ended mode (continued)

In a typical computer sound channel operating at 5 V, bridging raises the power into an 8-Ω speaker from a

singled-ended (SE, ground reference) limit of 250 mW to 1 W. In sound power, that is a 6-dB improvement—

which is loudness that can be heard. In addition to increased power, there are frequency response concerns.

Consider the single-supply SE configuration shown in Figure 25. A coupling capacitor is required to block the

dc offset voltage from reaching the load. These capacitors can be quite large (approximately 33 µF to 1000 µF)

so they tend to be expensive, heavy, occupy valuable PCB area, and have the additional drawback of limiting

low-frequency performance of the system. This frequency limiting effect is due to the high-pass filter network

created with the speaker impedance and the coupling capacitance and is calculated with equation 8.

1

(8)

f

+

c

2pR C

L (C)

For example, a 68-µF capacitor with an 8-Ω speaker would attenuate low frequencies below 293 Hz. The BTL

configuration cancels the dc offsets, which eliminates the need for the blocking capacitors. Low-frequency

performance is then limited only by the input network and speaker response. Cost and PCB space are also

minimized by eliminating the bulky coupling capacitor.

V

DD

–3 dB

V

O(PP)

C

(C)

V

O(PP)

R

L

f

c

Figure 25. Single-Ended Configuration and Frequency Response

Increasing power to the load does carry a penalty of increased internal power dissipation. The increased

dissipation is understandable considering that the BTL configuration produces 4× the output power of the SE

configuration. Internal dissipation versus output power is discussed further in the crest factor and thermal

considerations section.

single-ended (stereo) operation

In SE (stereo) mode (see Figure 24 and Figure 25), the load is driven from the primary amplifier output for each

channel (LO and RO, terminals 6 and 10).

The amplifier switches to single-ended operation when the ST/MN terminal is held high.

input operation

The input allows stereo inputs to be applied to the amplifier. When the ST/MN terminal is held high, the inputs

(LIN and RIN) drive the outputs as LO and RO in stereo mode. When the ST/MN terminal is held low, the inputs

are surrounded internally to create the mono BTL signal, driving the outputs as MO+ and MO–.

15

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

APPLICATION INFORMATION

BTL amplifier efficiency

Class-AB amplifiers are inefficient. The primary cause of inefficiencies is the voltage drop across the output

stage transistors. There are two components of the internal voltage drop. One is the headroom or dc voltage

drop that varies inversely to output power. The second component is due to the sinewave nature of the output.

The total voltage drop can be calculated by subtracting the RMS value of the output voltage from V . The

DD

internal voltage drop multiplied by the RMS value of the supply current, I rms, determines the internal power

DD

dissipation of the amplifier.

An easy-to-use equation to calculate efficiency starts out as being equal to the ratio of power from the power

supply to the power delivered to the load. To accurately calculate the RMS and average values of power in the

load and in the amplifier, the current and voltage waveform shapes must first be understood. See Figure 26.

I

V

O

DD

I

DD(avg)

V

(LRMS)

Figure 26. Voltage and Current Waveforms for BTL Amplifiers

Although the voltages and currents for SE and BTL are sinusoidal in the load, currents from the supply are very

different between SE and BTL configurations. In an SE application the current waveform is a half-wave rectified

shape, whereas in BTL it is a full-wave rectified waveform. This means RMS conversion factors are different.

Keep in mind that for most of the waveform both the push and pull transistors are not on at the same time, which

supports the fact that each amplifier in the BTL device only draws current from the supply for half the waveform.

The following equations are the basis for calculating amplifier efficiency.

P

L

Efficiency of a BTL amplifier +

(9)

P

SUP

where

2

L

V

P

2R

LRMS

P

+

, andV

+

, therefore, P

1

+

L

LRMS

L

Ǹ

R

2

L

p

+

[cos(t)] ^p

0

2V

V

P

1

P

+

ŕ

P

+ V

I

avg

I

avg +

sin(t) dt

and

p

SUP

DD DD

DD

p R

L

R

L

0

therefore,

P

2 V

V

DD

p R

P

+

SUP

L

substituting P and P

into equation 9,

L

SUP

2

V

P

2 R

p V

L

P

Efficiency of a BTL amplifier +

+

4 V

2 V

V

P

DD

p R

L

where

Ǹ_{2 P R}

V

+

P

L

16

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

APPLICATION INFORMATION

BTL amplifier efficiency (continued)

therefore,

Ǹ_{2 P R}

p

L

h

+

(10)

BTL

4 V

DD

P = Power devilered to load

V

= Peak voltage on BTL load

avg = Average current drawn from the power supply

L

P

V

= Power drawn from power supply

I

V

SUP

DD

= RMS voltage on BTL load

= Power supply voltage

= Efficiency of a BTL amplifier

LRMS

DD

R = Load resistance

η

L

BTL

Table 2 employs equation 10 to calculate efficiencies for four different output power levels. Note that the

efficiency of the amplifier is quite low for lower power levels and rises sharply as power to the load is increased,

resulting in a nearly flat internal power dissipation over the normal operating range. Note that the internal

dissipation at full output power is less than in the half power range. Calculating the efficiency for a specific

systemisthekeytoproperpowersupplydesign. Forastereo1-Waudiosystemwith8-Ω loadsanda5-Vsupply,

the maximum draw on the power supply is almost 3.25 W.

Table 2. Efficiency vs Output Power in 5-V, 8-Ω BTL Systems

Output Power

(W)

Efficiency

(%)

Peak Voltage

(V)

Internal Dissipation

(W)

0.25

0.50

1.00

1.25

31.4

44.4

62.8

70.2

2.00

2.83

4.00

0.55

0.62

0.59

0.53

†

4.47

†

High peak voltages cause the THD to increase.

A final point to remember about Class-AB amplifiers (either SE or BTL) is how to manipulate the terms in the

efficiency equation to utmost advantage when possible. Note that in equation 10, V is in the denominator.

DD

This indicates that as V

goes down, efficiency goes up.

DD

crest factor and thermal considerations

Class-AB power amplifiers dissipate a significant amount of heat in the package under normal operating

conditions. AtypicalmusicCDrequires12dBto15dBofdynamicrange, orheadroomabovetheaveragepower

output, to pass the loudest portions of the signal without distortion. In other words, music typically has a crest

factor between 12 dB and 15 dB. When determining the optimal ambient operating temperature, the internal

dissipated power at the average output power level must be used. The TPA0233 data sheet shows that when

the TPA0233 is operating from a 5-V supply into a 4-Ω speaker, 4-W peaks are available. Converting watts to

dB:

P

W

4 W

1 W

P

+ 10Log

+ 6 dB

(11)

dB

P

ref

Subtracting the headroom restriction to obtain the average listening level without distortion yields

6 dB – 15 dB = –9 dB (15-dB crest factor)

6 dB – 12 dB = –6 dB (12-dB crest factor)

6 dB – 9 dB = –3 dB (9-dB crest factor)

6 dB – 6 dB = 0 dB (6-dB crest factor)

6 dB – 3 dB = 3 dB (3-dB crest factor)

17

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

APPLICATION INFORMATION

crest factor and thermal considerations (continued)

Converting dB back into watts:

PdBń10

P

+ 10

P

W

ref

(12)

+ 63 mW (18-dB crest factor)

+ 125 mW (15-dB crest factor)

+ 250 mW (9-dB crest factor)

+ 500 mW (6-dB crest factor)

+ 1000 mW (3-dB crest factor)

+ 2000 mW (15-dB crest factor)

This is valuable information to consider when attempting to estimate the heat dissipation requirements for the

amplifier system. Comparing the absolute worst case, which is 2 W of continuous power output with a 3-dB crest

factor, against 12-dB and 15-dB applications drastically affects maximum ambient temperature ratings for the

system. Table 3 shows maximum ambient temperatures and TPA0233 internal power dissipation for various

output-power levels.

Table 3. TPA0233 Power Rating, 5-V, 3-Ω, Mono

PEAK OUTPUT POWER

(W)

POWER DISSIPATION

(W)

MAXIMUM AMBIENT

TEMPERATURE

AVERAGE OUTPUT POWER

4

2 W (3-dB crest factor)

1000 mW (6-dB crest factor)

500 mW (9-dB crest factor)

250 mW (12-dB crest factor)

125 mW (15-dB crest factor)

63 mW (18-dB crest factor)

1.7

1.6

1.4

1.1

0.8

0.6

–3°C

6°C

24°C

51°C

78°C

96°C

Table 4. TPA0233 Power Rating, 5-V, 8-Ω, Stereo

PEAK OUTPUT POWER

(W)

POWER DISSIPATION

MAXIMUM AMBIENT

TEMPERATURE

AVERAGE OUTPUT POWER

(W)

2.5

1250 mW (3-dB crest factor)

1000 mW (4-dB crest factor)

500 mW (7-dB crest factor)

250 mW (10-dB crest factor)

0.55

0.62

0.59

0.53

100°C

94°C

97°C

102°C

The maximum dissipated power (P

for a 4-Ω load. As a result, this simple formula for calculating P

), is reached at a much lower output power level for an 8-Ω load than

Dmax

may be used for a 4-Ω application.

Dmax

2

2V

DD

(13)

P

+

Dmax

2

p R

L

However, in the case of a 4-Ω load, the P

The amplifier may therefore be operated at a higher ambient temperature than required by the P

for a 4-Ω load.

occurs at a point well above the normal operating power level.

Dmax

formula

Dmax

The maximum ambient temperature depends on the heat sinking ability of the PCB system. The derating factor

for the DGQ package is shown in the dissipation rating table. Converting this to Θ

:

JA

1

Θ

+

+ 58.48°CńW

(14)

JA

0.0171

Derating Factor

18

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

APPLICATION INFORMATION

crest factor and thermal considerations (continued)

To calculate maximum ambient temperatures, first consider that the numbers from the dissipation graphs are

per channel so the dissipated power needs to be doubled for two channel operation. Given Θ , the maximum

JA

allowable junction temperature, and the total internal dissipation, the maximum ambient temperature can be

calculated with the following equation. The maximum recommended junction temperature for the TPA0233 is

150°C. The internal dissipation figures are taken from the Power Dissipation vs Output Power graphs.

(15)

(

)

(

)

T Max + T Max * Θ

P

+ 150 * 58.48 0.8 2 + 56°C 15-dB crest factor

A

J

JA

D

NOTE:

Internal dissipation of 0.8 W is estimated for a 2-W system with 15-dB crest factor per channel.

Tables 3 and 4 show that for some applications no airflow is required to keep junction temperatures in the

specified range. The TPA0233 is designed with thermal protection that turns the device off when the junction

temperature surpasses 150°C to prevent damage to the IC. Tables 3 and 4 were calculated for maximum

listening volume without distortion. When the output level is reduced the numbers in the table change

significantly. Also, using 8-Ω speakers dramatically increases the thermal performance by increasing amplifier

efficiency.

ST/MN (stereo/mono) operation

The ability of the TPA0233 to easily switch between mono BTL and stereo SE modes is one of its most important

cost saving features. This feature eliminates the requirement for an additional headphone amplifier in

applications where an internal speaker is driven in BTL mode but external stereo headphone or speakers must

be accommodated. When ST/MN is held high, the RIN and LIN inputs drive the output as Lo and Ro in stereo

SE mode. When ST/MN is held low, the inputs are summed internally and the output is driven as Mo+ and Mo–

in mono BTL mode. Control of the ST/MN input can be from a logic-level CMOS source or, more typically, from

a switch-controlled resistor divider network as shown in the functional block diagram.

19

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TPA0233

2-W MONO AUDIO POWER AMPLIFIER

WITH HEADPHONE DRIVE

SLOS278D – JANUARY 2000 – REVISED NOVEMBER 2002

MECHANICAL DATA

DGQ (S-PDSO-G10)

PowerPAD PLASTIC SMALL-OUTLINE PACKAGE

0,27

0,17

M

0,50

10

0,25

6

Thermal Pad

(See Note D)

0,15 NOM

3,05

2,95

4,98

4,78

Gage Plane

0,25

0°–ā6°

1

5

0,69

0,41

3,05

2,95

Seating Plane

0,10

0,15

0,05

1,07 MAX

4073273/A 04/98

NOTES: A. All linear dimensions are in millimeters.

B. This drawing is subject to change without notice.

C. Body dimensions do not include mold flash or protrusion.

D. The package thermal performance may be enhanced by bonding the thermal pad to an external thermal plane.

This pad is electrically and thermally connected to the backside of the die and possibly selected leads.

PowerPAD is a trademark of Texas Instruments.

20

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

PACKAGE OPTION ADDENDUM

www.ti.com

18-Apr-2006

PACKAGING INFORMATION

Orderable Device

Status ⁽¹⁾

Package Package

Pins Package Eco Plan ⁽²⁾Lead/Ball Finish MSL Peak Temp ⁽³⁾

Qty

Type

Drawing

TPA0233DGQ

ACTIVE

MSOP-

Power

PAD

DGQ

10

80 Green (RoHS & CU NIPDAU Level-1-260C-UNLIM

no Sb/Br)

TPA0233DGQG4

TPA0233DGQR

ACTIVE

MSOP-

Power

PAD

DGQ

80 Green (RoHS & CU NIPDAU Level-1-260C-UNLIM

no Sb/Br)

MSOP-

Power

PAD

2500 Green (RoHS & CU NIPDAU Level-1-260C-UNLIM

no Sb/Br)

TPA0233DGQRG4

MSOP-

Power

PAD

2500 Green (RoHS & CU NIPDAU Level-1-260C-UNLIM

no Sb/Br)

⁽¹⁾The marketing status values are defined as follows:

ACTIVE: Product device recommended for new designs.

LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.

NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in

a new design.

PREVIEW: Device has been announced but is not in production. Samples may or may not be available.

OBSOLETE: TI has discontinued the production of the device.

(2)

Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check

http://www.ti.com/productcontent for the latest availability information and additional product content details.

TBD: The Pb-Free/Green conversion plan has not been defined.

Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements

for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered

at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.

Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and

package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS

compatible) as defined above.

Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame

retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)

(3)

MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder

temperature.

Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is

provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the

accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take

reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on

incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited

information may not be available for release.

In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI

to Customer on an annual basis.

Addendum-Page 1

IMPORTANT NOTICE

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enhancements, improvements, and other changes to its products and services at any time and to

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TI warrants performance of its hardware products to the specifications applicable at the time of sale in

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TI assumes no liability for applications assistance or customer product design. Customers are responsible

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